WO2005008872A1 - Freischwingender sperrwandler mit strom- und spannungsbegrenzung - Google Patents
Freischwingender sperrwandler mit strom- und spannungsbegrenzung Download PDFInfo
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- WO2005008872A1 WO2005008872A1 PCT/EP2004/001924 EP2004001924W WO2005008872A1 WO 2005008872 A1 WO2005008872 A1 WO 2005008872A1 EP 2004001924 W EP2004001924 W EP 2004001924W WO 2005008872 A1 WO2005008872 A1 WO 2005008872A1
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- primary
- power supply
- voltage
- switch
- switched
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3385—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement with automatic control of output voltage or current
Definitions
- the present invention relates to a switching power supply, in particular to a switching power supply with a primary side and a secondary side, which has a transformer with a primary-side winding, a secondary-side winding and at least one auxiliary winding.
- the primary-side winding and the auxiliary winding are connected to the primary side and the secondary-side winding is connected to the secondary side.
- the switched-mode power supply has a primary-side switch which is connected to the primary-side winding in order to interrupt a current flow through the primary-side winding, a free-running circuit for generating switching pulses which drive the primary-side switch, and a circuit for generating an image voltage between the Connections of the auxiliary winding in order to generate an image voltage which depicts a voltage to be regulated on the secondary side on the primary side.
- Switched-mode power supplies are used in numerous electronic devices in order to generate the low-voltage direct voltage required to supply the electronic components from a mains voltage. Switched-mode power supplies have prevailed over conventional power supplies with power transformers in many applications, since they have a better efficiency from a certain performance class and in particular require less space.
- a high-frequency alternating voltage is transformed, which, for example, can be in the range from 20 kHz to 200 kHz instead of the usual mains frequency of 50 Hz or 60 Hz. Since the required number of turns of the transformer is inversely proportional to the frequency, the copper losses can be greatly reduced and the actual transformer is significantly smaller.
- switched-mode switching power supplies are known in which the frequency generated on the primary side of the high-frequency transformer by the switch, for example a bipolar transistor, is regulated as a function of the load present on the secondary side of the power supply regulate the transmitted power.
- the feedback required for such a regulation is realized, for example, by using a voltage tapped on an auxiliary winding as a controlled variable.
- a corresponding method for regulating the output current and / or the output voltage is described in EP 1 146 630 A2 and includes the same energy being loaded into the transformer with each pulse.
- the circuit arrangement shown in this document has the disadvantage of being comparatively complex since a relatively complex integrated circuit is used as the control circuit.
- the object on which the present invention is based is to provide a generic switched-mode power supply which, with reduced complexity, enables improved control characteristics and increased flexibility with regard to the operating parameters.
- This object is achieved by a switching power supply with the features of patent claim 1.
- Advantageous developments of the switching power supply according to the invention are the subject of several subclaims.
- the present invention is based on the finding that with the aid of a timing control unit which is coupled to the primary-side switch in such a way that the duration of a switch-off time of the primary-side switch can be set, in particular extended, within a switching cycle, a low switching frequency can be maintained at a low load and this enables precise voltage regulation and the setting of various output current characteristics.
- the switching power supply according to the invention is constructed from a few inexpensive components.
- the switched-mode power supply according to the invention thus offers the advantage of low costs with, at the same time, precise output voltage regulation, low no-load input power, and extremely variable replaceability.
- the switching power supply according to the invention also has the advantage of short-circuit protection.
- the time control unit has a drive capacitor, via whose charging current the switch-off time of the switch on the primary side can be set.
- the switch-off duration of the primary-side switch can be extended in a particularly simple manner via the drive capacitor.
- the transmitted power is thus set in such a way that the output voltage is almost independent of the load.
- the detection of the output voltage on the primary side is facilitated in that the transmitted energy is the same with each pulse, so that there is always a relatively long time during which current flows in the secondary winding. Short voltage peaks that arise due to leakage inductance can be filtered out with the aid of RC elements in the switching power supply according to the invention.
- a controlled charging current for the drive capacitor can be achieved in a particularly effective manner by means of a charging current control circuit which is arranged between the input connection of the switching power supply and the control connection of the primary-side switch.
- a vibration suppression circuit can be provided in order to suppress undesirable vibrations in the control circuit of the primary-side switch and thereby to increase the control accuracy.
- a phase shift circuit can be provided for phase-shifted switching off of the primary-side switch in order to accelerate the switching-off process of the primary-side switch and thereby increase the efficiency of the entire switching power supply.
- the time control unit is designed such that a control signal can be deactivated during a switch-on time of the primary-side switch.
- the switched-mode power supply according to the invention has two auxiliary windings on the primary side, with the aid of which the switch-off duration of the primary-side switch can also be controlled. This enables low switching frequencies at low loads and a decreasing power loss when idling.
- the secondary voltage can be determined relatively precisely on the primary auxiliary windings.
- auxiliary windings is connected to the primary-side switch via a diode and a transistor, then a current can be fed in at the anode of the diode, with which the switch-on time of the transistor is extended without influencing the switch-off threshold.
- a negative voltage is generated at the anode of the diode.
- the series connection consisting of two diodes or two resistors can also be used. An additional resistor can be provided to limit the peak current for the diode.
- auxiliary windings is connected to a capacitor via a second diode so that it can be charged to the voltage to be regulated on the secondary side and that, depending on the voltage across the capacitor, a current through the diode, a resistor, a third diode and the base-emitter path of the transistor flows, which delays the switching on of the primary-side switch by means of the on-time of the transistor, a voltage-controlled setting of the off-time of the primary-side switch can take place.
- RC elements which are connected to a control connection of the primary-side switch and to the first auxiliary winding, can enable a relatively low-resistance switchover with a relatively low holding current in the control circuit.
- the primary-side switch can also be switched on with a delay, since the energy in the capacitor is only slowly dissipated. This enables continuous adaptation to the load.
- An overvoltage protection circuit can be used to improve the control behavior at very low loads. With this circuit, the drive capacitors are discharged faster and charged more slowly as the output voltage increases. This enables very long pause times, which are automatically extended when the output voltage increases. This circuit acts as overvoltage protection and prevents a dangerous rise in the output voltage in the event of a simple fault.
- the charging current control circuit has a first zener diode, which is connected via a resistor to the base of a drive transistor in such a way that the on-time of the drive transistor delays the switching on of the primary-side switch.
- the main switch can be switched off by a Zener diode, which limits the voltage at the series circuit of the base-emitter path of the main switch with a resistor.
- the Z voltage limits the voltage at the series circuit of the base-emitter path of the main switch with a resistor.
- the temperature dependence of the output current can be reduced in a simple manner with the aid of a temperature compensation circuit.
- the voltage control can be carried out by means of an optocoupler and a secondary control circuit.
- the optocoupler is controlled so that it is conductive when the control voltage is undershot.
- the switching power supply runs at maximum frequency, the frequency being limited by a resistor connected in series with the optocoupler.
- the optocoupler is blocked to such an extent that the switching frequency drops to the frequency required to maintain the control voltage at the output. If the optocoupler is completely blocked, the switching frequency returns to the minimum frequency at which only a very low power is transmitted. In this state, the power consumed by the circuit is very low, and it is thus possible to keep the voltage ripple relatively low, even in idle, despite the very low idle input power.
- Figure 1 is a block diagram of a primary controlled switching power supply according to the present invention
- Figure 2 is a circuit diagram of a primary controlled switching power supply according to a first embodiment
- FIG. 3 shows a circuit diagram of a switching power supply according to a second embodiment
- Figure 4 is a circuit diagram of a switching power supply according to a third embodiment
- Figure 5 is a circuit diagram of a switching power supply according to a fourth embodiment
- Figure 6 is a circuit diagram of a switching power supply according to a fifth embodiment.
- Figure 1 shows schematically a block diagram of a switching power supply according to the present invention.
- the switching power supply 100 is supplied with the AC voltage U EI N, which can be, for example, the line voltage, at the input. In Europe, the mains voltage varies between 180 V to 264 V AC, in America between 90 V and 130 V AC.
- the input voltage is rectified and stabilized. It also ensures that interference signals that are generated in the switching power supply do not get into the AC network.
- the primary-side winding 110 of the insulating transformer 108 and the primary-side switch 104 which is a transistor here, form a series circuit which is connected to the rectified input voltage.
- the primary-side switch 104 interrupts the current which flows through the primary-side winding 110 in accordance with the control signals of the drive circuit 106.
- the switching pulses supplied by the control circuit to the control input of the primary-side switch 104 are controlled by the block 116, in which the controlled variable is generated with the aid of an auxiliary winding 114 of the transformer 108.
- the two signal paths 120 and 122 designate two essential functions of the block 116: On the one hand, the signal 120 "pumps" the control circuit 106 in order to maintain the free oscillation. On the other hand, the signal path 122 controls the control circuit 106 in such a way that changes in the Switching cycle affect the electrical power supplied to the transformer 108 in a desired manner.
- control circuit 106 contains a time control unit 107 for this purpose, which ensures that the length of the pause times (or also switch-off times) in which the primary-side switch 104 is open is adapted to the required power. The energy that is supplied to the transformer during each switch-on phase of the primary switch remains the same.
- the secondary-side winding 112 of the transformer 108 is connected to a block 118 which generates the secondary-side voltage U AUS and, if necessary, stabilizes it.
- the mode of operation of the embodiment of the galvanically isolated switching power supply according to the invention shown schematically in FIG. 1 will be explained in more detail below.
- the control circuit 106 controls the primary-side switch 104 in such a way that it is alternately brought into the conductive and non-conductive state. Due to the voltage supplied by block 102, a current flows into primary winding 110 whenever primary switch 104 is in the conductive state. A change in current stores energy in the magnetic field of transformer 108. When the primary switch 104 blocks, the energy stored in the magnetic field is primarily discharged through the secondary winding 112 and in block 118 which generates and stabilizes the secondary voltage. A small portion of the energy is also discharged into block 116 through auxiliary winding 114. As a controlled variable, this generates an auxiliary voltage. The energy discharges periodically, but rectification and filtering can produce an essentially rectified voltage as an auxiliary voltage become. Since the magnetic coupling between the different windings of the transformer 108 is constant and does not depend on the values of the current or the voltage, the value of the auxiliary voltage is proportional to the value of the secondary voltage and thus to the value of the output voltage.
- the switch-off duration of the primary-side switch 104 can be set such that the energy fed into the transformer depends on the output voltage.
- the transmitted power is thus set so that there is an almost load-independent output voltage U OUT .
- the detection of the output voltage on the primary side is facilitated in that the transmitted energy is the same for each pulse, so that there is always a relatively long time during which current flows in the auxiliary winding 114.
- FIG. 2 A circuit diagram of a possible form of implementation of the switching power supply according to the invention is shown in FIG. 2. It is essential in this circuit that the switch-off time of the primary-side switch, here of the transistor T12, can be extended via the corresponding control of the transistor T11.
- the capacitor C15 is charged via the resistors R11 and R12. If the voltage is sufficient, a current flows through the resistor R18, the base-collector path of the transistor T11, the resistor R20, the base-emitter stretcher of the transistor T12, the resistor R23 and the diode D17.
- the primary-side switch T12 is thereby opened, and a current flows through the primary main winding of the transformer W10 (connection 4 / connection 1).
- a voltage is induced on the auxiliary winding of the transformer (connection 3 / connection 2), which causes positive coupling via the capacitor C15, the resistor R23 and the capacitance C14 and accelerates the switch-on process of the primary-side switch T12.
- the current flowing through the primary-side main winding, the primary-side switch T12, the resistor R23 and the diode D17 increases. This also increases the voltage drop across resistor R23, and thus the base-emitter voltage of transistor T13.
- the base-emitter voltage of transistor T13 exceeds the threshold voltage, the collector-emitter path of T13 becomes conductive and in the As a result, the transistor T12 is switched off.
- the current flow in the primary winding of the transformer is interrupted and, due to the self-induction, the voltages on the windings of the transformer are reversed. An induced current flows both in the secondary winding and in the auxiliary winding.
- the current in the secondary winding charges the capacitor C100 and generates a voltage that can be used at the output.
- the current in the auxiliary winding charges the capacitor C15 via the diode D15 and the resistor R13 to a voltage which corresponds to the voltage at the capacitor C100, converted via the number of turns ratio of the auxiliary winding to the secondary winding. That is, an image of the output voltage dropping across capacitor C100 is produced on capacitor C15.
- the current in the auxiliary winding also accelerates the switching off of the transistor T12 via the capacitor C14.
- transistor T10 When the voltage drop across capacitor C15 is less than the sum of the threshold voltages of diode D16 and transistor T10, transistor T10 is off and transistor T11 is on so that capacitor C14 is connected in series across resistor R18 , the transistor T12 and the resistor R20 is charged quickly.
- the primary-side switch T12 is thus switched on again after a brief pause and a new cycle begins.
- the transistor T10 becomes conductive and thus reduces the base current of the transistor T11, so that it limits the charging current of the capacitor C14 and thus the switch-off duration of the primary-side switch T12 extended.
- the transmitted power can therefore be adapted to the output voltage in a particularly simple manner by setting the switch-off duration, regardless of the connected load.
- the detection of the output voltage is facilitated by the fact that the transmitted energy is the same for each pulse, so that there is always a relatively long time during which current flows in the secondary winding.
- Short voltage peaks that arise due to leakage inductances can be filtered out with appropriately dimensioned RC elements R13, C13, R14, D14, as shown in FIG. 3. This creates the image tension the capacitor C15 is a very accurate representation of the voltage drop across the capacitor C100.
- the output current is limited by the maximum frequency that can be set using resistors R18 and R20. This determines the maximum credit point. When the maximum power point is exceeded, the output voltage drops and thus also the voltage that drops across the capacitor C15. This also causes the current through resistors R18 and R20 to decrease, and consequently the frequency and the transmitted power decrease. By changing the ratio of the resistance values R18 to R20, the dependence of the output current on the output voltage can be set, so that different characteristic curves are possible.
- the embodiment shown in FIG. 2 still has a dependency of the output current on the input voltage, since the delay times at the primary-side switch T12 cause a maximum primary current that is dependent on the input voltage.
- FIG. 3 in which a second embodiment of the switching power supply according to the invention is shown, a capacitor C17 is connected to the emitter of the primary-side switch.
- the capacitance C18 can be replaced by a resistor.
- FIG. 3 components with the same designations as in FIG. 2 are provided with the same reference symbols. If, with the primary-side switch T12 switched off, the secondary current has dropped to 0, a voltage at the level of the output voltage U OUT plus the forward voltage of the diode D100 is present at the secondary-side winding. The parasitic capacitances are charged with this voltage.
- the voltage of the auxiliary winding according to the expanded embodiment shown in FIG. 3 is controlled by a capacitor C13, the resistance R14, the diode D14 and the resistor R 13 filter formed to the capacitor C14.
- FIG. 3 also provides a delay element formed by the capacitor C16, the resistor R21, the resistor R22 and the capacitor C18, which delays the rise in the base-emitter voltage on the transistor T13 due to the voltage rise across the resistor R23.
- This delay element is not absolutely necessary for the functioning of the circuit, but increases the efficiency, since the switch-off process of the transistor C12 is accelerated due to the phase shift.
- a second auxiliary winding can be provided for power regulation.
- the switched-mode power supply shown in FIG. 4 with electrical isolation between the primary and secondary parts also represents a freely oscillating flyback converter.
- a resistance R124 turns a negative on the anode of the diode D119 via the resistor R124 on the anode of the primary-side switch T110 Creates tension.
- a diode could also be used instead of the resistor R124.
- a current can be fed in at the anode of the diode D119, with which the switch-on time of the transistor T111 is extended without influencing the switch-off threshold.
- Control of the switch-off duration of the transistor T110 is thus possible. This leads to a low switching frequency at low load, and the power loss at idle and at low load decreases.
- the secondary voltage can be determined relatively accurately using the primary auxiliary windings.
- the RC element R125, C118 filters out the induced voltage peaks of the leakage inductance and thus improves the control behavior.
- the resistor R125 serves to limit the peak current to protect the diode D121.
- the parallel connection of the RC elements C113, R115 and C114, R116 brings about a low-resistance switching of the transistor T111 with a relatively low holding current.
- the transistor T110 can be switched on with a delay since the energy in the capacitor 114 is only slowly dissipated. This means that the duration of the break can be continuously adapted to the load.
- the control behavior can be improved with a very low load with the aid of the diode D114 of the capacitance C117, the diode 115 and the resistor R120 or the diode D116.
- the capacitors C113 and C114 are discharged faster and charged more slowly as the output voltage increases. This allows very long pause times, which are automatically extended when the output voltage increases.
- This circuit also acts as overvoltage protection and prevents the output voltage U A us from rising dangerously in the event of a simple fault.
- the induced voltage peaks of the leakage inductance can be filtered out, whereby the control behavior can be further improved.
- the switch-on threshold of the transistor T111 can be adjusted via the resistor R118.
- the switch-on threshold of the transistor T111 can be adjusted to reduce the dependence of the output current on the input voltage.
- a temperature compensation circuit is provided to reduce the temperature dependency of the output current, which comprises the transistor T112, the resistor R128 and the resistor R127.
- Another embodiment of the switching power supply according to the invention will be explained below with reference to FIG. 5.
- the mode of operation of the circuit shown is the same as that of the circuits from FIGS. 2 and 3, with the difference that the circuit according to FIG. 5 manages with considerably fewer components because the charging current for the drive capacitor C213 is regulated more easily.
- the primary-side switch T12 is switched off by a Zener diode D214, which limits the voltage at the series connection of the base-emitter path of the primary-side switch T12 and the resistor R220.
- the Z voltage is reached, the current flow through the transistor T210 cannot increase any further, as a result the voltage at the transformer drops and the positive feedback causes the switch T12 on the primary side to be switched off quickly.
- FIG. 6 Another embodiment of the switching power supply according to the invention will now be described with reference to FIG. 6, in which an additional optocoupler is used to feed the output voltage back to the primary side.
- Various circuits for switched-mode power supplies with low idle input powers are known, which switch off the primary part of the power supply by means of an optocoupler when the output power falls below a predetermined level, thereby enabling a very low input power.
- the disadvantage of this known principle is that the idle voltage has a very high ripple voltage.
- the voltage control can be carried out by means of the optocoupler IC10 and a control circuit on the secondary side.
- the IC10 optocoupler is controlled so that it is conductive when the control voltage is undershot.
- the switching power supply operates below the control voltage at the maximum frequency, the frequency being limited by a resistor R415 connected in series with the optocoupler IC10.
- the optocoupler IC10 is blocked so far that the switching frequency drops to the frequency that is required to maintain the control voltage at the output. If the optocoupler IC 10 is completely blocked, the switching frequency goes back to the minimum frequency at which only a very low power is transmitted. In this state, the power consumed by the circuit is very low. This makes it possible to keep the voltage ripple relatively low even when idling, despite the very low idle input power.
- Current limitation can be implemented on the secondary side and use the same optocoupler IC10.
- the current limitation can also be implemented on the primary side.
- a voltage from the auxiliary winding W10 2-3 is used to control the primary-side switch T12 via the optocoupler IC10 and the series resistor R415, which voltage is proportional to the output voltage.
- the output voltage drops, the charging current of the capacitor C414 drops and the frequency drops. Less power is transmitted and the output current remains almost constant. Different output characteristics are possible due to different dimensions. What they all have in common is that the short-circuit current is very low, since the optocoupler is blocked in the short-circuit.
- the minimum frequency and thus the minimum power when the optocoupler is blocked and the maximum frequency when the optocoupler is conductive are achieved here.
- the current is regulated by controlling the switching frequency as a function of the output voltage transmitted by an auxiliary winding.
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2006519774A JP4260840B2 (ja) | 2003-07-15 | 2004-02-26 | 電流制限と電圧クランプとを有する自由発振フライバックコンバータ |
US10/520,298 US7295449B2 (en) | 2003-07-15 | 2004-02-26 | Simple switched-mode power supply with current and voltage limitation |
BRPI0405638A BRPI0405638B1 (pt) | 2003-07-15 | 2004-02-26 | fonte de alimentação em modo de comutação simples com limitação de corrente e tensão |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
EP03016065.9 | 2003-07-15 | ||
EP03016065A EP1499005B1 (de) | 2003-07-15 | 2003-07-15 | Freischwingender Sperrwandler mit Strom- und Spannungsbegrenzung |
Publications (1)
Publication Number | Publication Date |
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WO2005008872A1 true WO2005008872A1 (de) | 2005-01-27 |
Family
ID=33462127
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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PCT/EP2004/001924 WO2005008872A1 (de) | 2003-07-15 | 2004-02-26 | Freischwingender sperrwandler mit strom- und spannungsbegrenzung |
Country Status (10)
Country | Link |
---|---|
US (1) | US7295449B2 (de) |
EP (2) | EP1499005B1 (de) |
JP (1) | JP4260840B2 (de) |
CN (1) | CN100435465C (de) |
AT (2) | ATE408926T1 (de) |
BR (1) | BRPI0405638B1 (de) |
DE (2) | DE50310517D1 (de) |
DK (1) | DK1499005T3 (de) |
ES (2) | ES2314311T3 (de) |
WO (1) | WO2005008872A1 (de) |
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- 2003-07-15 ES ES04010468T patent/ES2314311T3/es not_active Expired - Lifetime
- 2003-07-15 ES ES03016065T patent/ES2249662T3/es not_active Expired - Lifetime
- 2003-07-15 EP EP03016065A patent/EP1499005B1/de not_active Expired - Lifetime
- 2003-07-15 DE DE50301019T patent/DE50301019D1/de not_active Expired - Lifetime
- 2003-07-15 AT AT04010468T patent/ATE408926T1/de active
- 2003-07-15 AT AT03016065T patent/ATE302500T1/de active
- 2003-07-15 EP EP04010468A patent/EP1501179B1/de not_active Expired - Lifetime
- 2003-07-15 DK DK03016065T patent/DK1499005T3/da active
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- 2004-02-26 CN CNB2004800232893A patent/CN100435465C/zh not_active Expired - Fee Related
- 2004-02-26 BR BRPI0405638A patent/BRPI0405638B1/pt not_active IP Right Cessation
- 2004-02-26 US US10/520,298 patent/US7295449B2/en not_active Expired - Lifetime
- 2004-02-26 WO PCT/EP2004/001924 patent/WO2005008872A1/de active Application Filing
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US8023290B2 (en) | 1997-01-24 | 2011-09-20 | Synqor, Inc. | High efficiency power converter |
US8493751B2 (en) | 1997-01-24 | 2013-07-23 | Synqor, Inc. | High efficiency power converter |
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US10199950B1 (en) | 2013-07-02 | 2019-02-05 | Vlt, Inc. | Power distribution architecture with series-connected bus converter |
US10594223B1 (en) | 2013-07-02 | 2020-03-17 | Vlt, Inc. | Power distribution architecture with series-connected bus converter |
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US11705820B2 (en) | 2013-07-02 | 2023-07-18 | Vicor Corporation | Power distribution architecture with series-connected bus converter |
Also Published As
Publication number | Publication date |
---|---|
CN1836365A (zh) | 2006-09-20 |
ES2314311T3 (es) | 2009-03-16 |
EP1499005A1 (de) | 2005-01-19 |
DE50301019D1 (de) | 2005-09-22 |
EP1501179B1 (de) | 2008-09-17 |
JP2007507197A (ja) | 2007-03-22 |
CN100435465C (zh) | 2008-11-19 |
BRPI0405638A (pt) | 2005-06-28 |
EP1499005B1 (de) | 2005-08-17 |
US20060133117A1 (en) | 2006-06-22 |
DE50310517D1 (de) | 2008-10-30 |
DK1499005T3 (da) | 2005-10-24 |
ATE408926T1 (de) | 2008-10-15 |
BRPI0405638B1 (pt) | 2016-03-01 |
ES2249662T3 (es) | 2006-04-01 |
US7295449B2 (en) | 2007-11-13 |
JP4260840B2 (ja) | 2009-04-30 |
ATE302500T1 (de) | 2005-09-15 |
EP1501179A1 (de) | 2005-01-26 |
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