WO1999057801A1 - Inverter circuit with avalanche current prevention - Google Patents

Inverter circuit with avalanche current prevention Download PDF

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Publication number
WO1999057801A1
WO1999057801A1 PCT/US1999/007744 US9907744W WO9957801A1 WO 1999057801 A1 WO1999057801 A1 WO 1999057801A1 US 9907744 W US9907744 W US 9907744W WO 9957801 A1 WO9957801 A1 WO 9957801A1
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WO
WIPO (PCT)
Prior art keywords
coupled
terminal
switching element
bias
circuit according
Prior art date
Application number
PCT/US1999/007744
Other languages
French (fr)
Inventor
Mihail S. Moisin
Original Assignee
Electro-Mag International, Inc.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Electro-Mag International, Inc. filed Critical Electro-Mag International, Inc.
Priority to EP99915338A priority Critical patent/EP1092262A1/en
Priority to AU33876/99A priority patent/AU3387699A/en
Priority to CA002331376A priority patent/CA2331376A1/en
Publication of WO1999057801A1 publication Critical patent/WO1999057801A1/en

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/081—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit
    • H03K17/0814—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the output circuit
    • H03K17/08146—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the output circuit in bipolar transistor switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to circuits having switching elements and more particularly, to a circuit having switching elements biased by inductive circuit elements.
  • An inverter circuit adapted for operation at or near a resonant frequency of the circuit.
  • An inverter circuit changes direct current (DC) power to alternating current (AC) power.
  • An illustrative inverter circuit includes first and second switching elements coupled in a half-bridge configuration. The switching elements are controlled to facilitate resonant operation of the circuit.
  • a circuit path to a load energized by the inverter circuit includes resistive, inductive and capacitive circuit elements coupled in various series and parallel arrangements.
  • Inverter circuits generally have diodes, known as free wheeling or antiparallel diodes, coupled across terminals of the switching elements such that the diodes are biased into a conduction state when the switching element is biased into its non-conduction state and vice-versa. These diodes become conductive for a period of time during which none of the bridge switching elements are conductive. This time is commonly referred to as dead time. During the dead time, the free wheeling diodes provide a discharge path for energy stored in the resonant inductive and capacitive circuit elements. As known to one of ordinary skill in the art, if the charge stored in the circuit elements is not provided with a discharge path, the energy will resonate in parasitic capacitive and inductive circuit elements. Such resonance will generate high voltages and frequencies that could destroy circuit elements.
  • the free wheeling diodes provide a discharge path during the dead time, these diodes do not prevent avalanche current flow through the switching elements.
  • the voltage drop across a conductive free wheeling diode can reverse bias a switching element thereby facilitating avalanche current flow through the switching element.
  • the undesirable avalanche current flow can damage the switching element and may reduce the reliability of the switching element and any circuit which includes the switching element.
  • Avalanche current flow will also slow switching element transitions between conductive and non-conductive states due to the time required for the stored energy from the avalanche current to discharge.
  • the present invention provides a circuit that reduces or eliminates avalanche current flow through circuit switching elements. Although the circuit is primarily shown and described as a resonant inverter circuit, it is understood that the circuit has other applications as well.
  • a resonant inverter circuit in accordance with the present invention includes first and second switching elements with a first inductive element coupled therebetween.
  • a first freewheeling diode is coupled across the first switching element and a second freewheeling diode is coupled across the second switching element.
  • a first bias element having an inductive impedance characteristic is coupled to the first switching element and a second bias element having an inductive impedance characteristic is coupled to the second switching element.
  • the first and second bias elements are inductively coupled to the first inductive element such that the bias elements reduce or eliminate avalanche current through a respective switching element.
  • each of the first and second switching elements are switched at a duty cycle slightly less than fifty percent.
  • the first switching element is conductive for about one-half of a resonant cycle as current flows in a first direction and the second switching element is conductive for the other half of the resonant cycle as current flows in an opposite direction. If the first and second switching elements are simultaneously conductive, the positive and negative rails of the inverter are shorted together. This is referred to as cross conduction.
  • cross conduction To prevent cross conduction, there is a period of time known as dead time where the first and second switching elements are non-conductive. During the dead time, one of the first and second freewheeling diodes provides a
  • the first bias element negates reverse biasing of the first switching element by a voltage drop across the conductive first diode. By preventing reverse biasing of the first switching element, avalanche current flow can be reduced or in some instances eliminated.
  • the second bias element prevents or eliminates avalanche current flow through the second switching element as the second diode conducts current.
  • Figure 1 is a circuit diagram of an exemplary circuit in accordance with the present invention
  • Figure 2 is a circuit diagram of a part of the circuit of Figure 1 ;
  • FIG. 3 is a further embodiment of a circuit in accordance with the present invention.
  • Figure 4 is another embodiment of a circuit in accordance with the present invention.
  • Figure 5 is a circuit diagram of an exemplary embodiment of a part of the circuit of Figure 4.
  • the inverter circuit 100 includes first and second switching elements 101a, 101b here shown as transistor switches Ql ,Q2, coupled in a half-bridge configuration.
  • the first switching element Ql is coupled to a positive rail 102 of the inverter and the second switching element Q2 is coupled to a negative rail 104.
  • Coupled between the first and second switching elements Q1,Q2 are a resonant inductive element LR and a resonant capacitive
  • a load 106 such as a fluorescent lamp, is coupled in parallel with the resonant capacitive element CP.
  • the circuit 100 can also include a first bridge capacitor CB1 coupled in between the load 106 and the positive rail 102 and a second bridge capacitor CB2 coupled between the load and the negative rail 104.
  • the first and second switching elements 101a, b can be formed from bipolar junction transistors (BJTs), field effect transistors (FETs), or other switching elements known to one of ordinary skill in the art.
  • the switching elements 101a, 101b can also be formed from a plurality of switching elements and/or integrated circuits.
  • the first switching element Ql is a BJT with a first or collector terminal 108 coupled to the positive rail 102, a second or base terminal 110 coupled to a first control circuit 114 and a third or emitter terminal 112 coupled to a first terminal of a first inductive element LQl.
  • a collector terminal 116 of the second switching element Q2 is coupled to a second terminal of the resonant inductive element LR, a base terminal 118 is coupled to a second control circuit 120 and an emitter terminal 122 is coupled to a second inductive element LQ2.
  • the second inductive element LQ2 is coupled between the emitter terminal 122 of the second switching element Q2 and the negative rail 104.
  • the first and second control circuits 104,106 control the conduction state of the respective first and second switching elements Q1,Q2 to facilitate resonant operation of the inverter circuit 100.
  • Exemplary control circuits for controlling the switching elements Q1,Q2 are disclosed in U.S. Patent Nos. 5, 124,619 (Moisin et al.), 5, 138,234 (Moisin), and 5, 138,236 (Bobel et al.), all incorporated herein by reference.
  • first diode Dl Coupled across the first switching element Ql is a first diode Dl, commonly referred to as a free wheeling or antiparallel diode.
  • a second free wheeling diode D2 is coupled across the second switching element Q2.
  • the first inductive element LQl is coupled between an anode 124 of the first free wheeling diode Dl and the emitter terminal 112 of the first switching element Ql.
  • a cathode 126 of the first diode Dl is coupled to the collector terminal 108 of the first switching element Ql .
  • the second free-wheeling diode D2 has a cathode 128 coupled to the collector terminal 116 of the second switching element Q2 and an anode 130 coupled to the second inductive element LQ2.
  • the second inductive element LQ2 is coupled between the anode 130 of the second diode D2 and the emitter terminal 1-22 of the second switching element Q2.
  • the anode 130 is also coupled to the negative rail 104 of the inverter.
  • the first and second inductive elements LQ1,LQ2 are inductively coupled to the resonant inductive element LR.
  • the first inductive element LQl has a polarity indicated by a dot as shown, in accordance with conventional dot notation.
  • the second inductive element LQ2 has a polarity as indicated by a dot as shown.
  • the dot indicates a rise in voltage from the unmarked to the marked terminal. For example, current flowing into the dot on a primary side of a transformer has a positive polarity.
  • the first and second inductive elements LQ1,LQ2 reduce or eliminate avalanche current flow from the respective collector terminals
  • the inverter circuit operates at or near a characteristic resonant frequency of the circuit with the first and second switching elements Q1,Q2 alternately conducting current. It is understood that the switching elements Q1,Q2 have a conductive or ON state in which current flows through the switching element and a non- conductive or OFF state in which state current does not flow through the switching element.
  • An inverter circuit driving a load having resistive, capacitive and inductive impedance characteristics is generally referred to a resonant inverter circuit.
  • the resistive, capacitive and inductive elements here the load 106, the resonant capacitive element CP and the resonant inductive element LR, determine the resonant frequency for the circuit.
  • a generally sinusoidal current flows to the load 106.
  • the AC load current flows through the resonant elements LR, CP and the load 106 in a first direction during a first part of a resonant cycle and in a second, opposite direction during a second part of the resonant cycle.
  • the first switching element Ql is conductive as the current flows in a direction from the resonant inductive element LR to the load 106 and the second switching element Q2 is conductive as current flows from the load 106 to the resonant inductive element LR.
  • the first and second switching elements Q1,Q2 should not be biased into their conductive states at the same time.
  • the switches provide a signal path having a relatively low resistance characteristic (e.g. , a short circuit) between the positive and negative rails 102,104.
  • a resultant current could destroy circuit elements.
  • the first and second control circuits Ql ,Q2 provide a period of time, referred to as dead time, where both the first and second switching elements Q1,Q2 are biased into their non-conduction or OFF state.
  • inductive and capacitive circuit elements e.g., LR, CP
  • energy stored in the inductive and capacitive circuit elements can produce one or more parasitic resonant signals having relatively high frequencies and relatively high voltages.
  • parasitic resonant signals may damage circuit elements exposed thereto.
  • a dissipation signal path is used to discharge the energy stored in circuit elements such as inductive element LR and capacitive element CP.
  • the first and second free wheeling diodes D1,D2 provide the dissipation circuit path through which circuit elements discharge stored energy during the dead time when both the first and second switching elements Q1,Q2 are OFF.
  • the order in which the switching elements Q1,Q2 and the diodes D1,D2 are conductive depends upon whether the load is underdamped or overdamped. If the load 106 is purely resistive, i.e., not underdamped or overdamped, the free wheeling diodes D1,D2 do not conduct. If the circuit operates at a frequency below the resonant frequency, i.e. , the load is underdamped, a conduction sequence is: first switching element Ql; first diode Dl; second switching element Q2; and second diode D2. For circuit operation at a frequency above resonance, i.e. , overdamped, the conduction sequence is: first diode Dl; first switching element Ql.; second diode D2; and second switching element Q2.
  • the reverse bias of the second switching element Q2 by diode D2 is counterbalanced by a potential of the second bias element LQ2 so that avalanche current does not flow from the collector 116 to the base 118 of the second switching element Q2.
  • the second bias element LQ2 applies a bias to the emitter 122 of the second switching element Q2 to prevent avalanche current flow by forcing the emitter to a potential that is more negative than the potential of the collector.
  • FIG. 2 shows the polarities of the bias elements LQ1,LQ2 with respect to the resonant inductive element LR as indicated with conventional dot notation. Voltage polarities are indicated with a " + " for a positive voltage and a "-" for a negative voltage. The respective voltage polarities for the inductive circuit elements LR,LQ1,LQ2 for current flow while Ql is ON are shown without parentheses. As Ql turns OFF, the voltage polarities switch and are shown in parentheses.
  • the switch in voltage polarity of the second switching element LQ2 provides a negative bias to the emitter 122 of the second switching element Q2. This negative bias offsets the reverse bias applied to the second switching element Q2 by the conductive second diode D2. By maintaining the emitter 122 at a lower voltage potential than the collector 116, avalanche current flow from the collector 116 to the base 118 of the second switching element Q2 is reduced or eliminated.
  • the first bias element LQl provides a negative bias to the emitter 112 of the first switching element Ql when the first diode Dl is conductive prior to the first
  • This circuit arrangement provides a more reliable circuit since the switching elements are not subject to avalanche current flow.
  • the switching elements Q1,Q2 are also more consistent in operation since they are not saturated and unknown times for charge stored in the collector-base junction to discharge are not required. Since energy is not stored in the collector-base junction, the switching element can transition between conduction states more rapidly. Further, the impedance provided by the first and second bias elements limits current flow through the first and second switching elements should cross conduction occur.
  • FIG. 3 shows a further embodiment of an inverter circuit, and in particular the first and second control circuits 114,120, in accordance with the present invention, wherein like reference designations represent like elements.
  • the first control circuit 114 is coupled to the base 110 of the first switching element Ql and includes a first resistor
  • the second control circuit 120 includes a second capacitor C2 coupled between the base and emitter terminals 118, 122 of the second switching element Q2.
  • a second resistor R2 is coupled between the base 118 of the second switching element Q2 and the negative rail 104 of the inverter. This arrangement references the base of the switching element Q2 to the negative rail, thus making the circuit less sensitive to parametric variations of the switching element, e.g., transistor.
  • FIG. 4 is another exemplary embodiment of a circuit 200 providing avalanche current prevention, wherein like reference designation indicate like elements .
  • FIG. 200 shows a part of an inverter circuit including first and second switching elements Ql ,Q2 coupled in a half bridge configuration.
  • the switching elements Ql ,Q2 are shown as npn transistors.
  • the first switching element Ql has a collector terminal 202 coupled
  • the first inductive bias element LQl has a first terminal 212 coupled to the emitter terminal 210 of the first switching element Ql and a second terminal 214 coupled to a first terminal 216 of a loop inductive element LQl A.
  • a first antiparallel diode Dl is coupled between a second terminal 218 of the loop inductive element LQ1A and the positive rail 204 of the inverter.
  • the second terminal 218 of the loop inductive element LQl A is also coupled to a resonant inductive element LR and a collector 220 of the second switching element Q2.
  • the first inductive bias element LQl is effective to reduce or prevent avalanche current from flowing through the first switching element Ql by forcing the emitter terminal 210 to a more negative potential than that of the collector terminal 202 when the first antiparallel diode Dl is conductive. This occurs immediately after the second switching element Q2 turns off but before the first switching element Ql turns on, i.e., the dead time. While the first inductive bias element LQl prevents avalanche current flow, the voltage across this inductive element tends to cause to a current flow through a circuit loop including the first diode Dl and the first switching element Ql . However, the loop inductive bias element LQl A is effective to limit or minimize the current flowing through this circuit loop. Looking to the respective polarities (indicated by conventional dot notation) of the first inductive bias element LQl and the loop inductive bias element
  • the loop inductive bias element LQl A therefore reduces the voltage that appears across the remainder of the circuit loop elements, e.g., the first diode Dl and the first switching element Ql . By reducing this voltage, the amount of current flowing through the Dl/Ql circuit loop is also reduced.
  • the impedance characteristics of the first inductive bias element LQl as compared with the loop inductive element LQl A can vary. In general, the number of turns of the loop inductive element LQl A is less than or equal to the number of turns of the first
  • the first inductive bias element LQl and the loop inductive element LQl A each have three turns.
  • FIG. 5 is an exemplary embodiment of the control circuit 208 of FIG. 4.
  • the control circuit includes a collector-base resistor RCB and a base resistor RB coupled in series between the positive rail 204 of the inverter and a point between the first inductive bias element LQl and the loop inductive element LQl A.
  • the base terminal 206 of the first switching element Ql is coupled to a node 207 between the series-coupled resistors RCB,RB.
  • a base-emitter capacitor CBE is coupled between the emitter terminal 210 and the node 207.
  • a base-emitter resistor RBE is also coupled between the emitter terminal 210 and the node 207.
  • the resulting R-C network is effective to control the conduction state of the first switching element Ql during resonant operation of the inverter circuit
  • inverter circuit of the present invention is not limited to the particular embodiments shown.
  • an inverter can be formed in a full bridge configuration with additional switching elements.
  • the configuration of the resonant inductive and capacitive elements and load can be coupled in various combinations such as parallel loaded (FIG. 1), series-parallel loaded, and various other arrangements known to one skilled in the art.

Abstract

An electronic circuit includes first and second inductive bias elements coupled to respective first and second switching elements for preventing avalanche current flow through the switching elements. In one embodiment, a resonant inverter circuit includes first and second switching elements with first and second freewheeling diodes coupled across the respective switching elements. A first inductive bias element is coupled to the first switching element and a second inductive bias element is coupled to the second switching element. The first and second bias elements are inductively coupled with a resonant inductive element for biasing the respective first and second switching elements against avalanche current flow.

Description

INVERTER CIRCUIT WITH AVALANCHE CURRENT PREVENTION
FIELD OF THE INVENTION
The present invention relates to circuits having switching elements and more particularly, to a circuit having switching elements biased by inductive circuit elements.
BACKGROUND OF THE INVENTION
Many electrical circuits include switching elements for controlling operation of the circuit. One such type of circuit, is an inverter circuit adapted for operation at or near a resonant frequency of the circuit. An inverter circuit changes direct current (DC) power to alternating current (AC) power. An illustrative inverter circuit includes first and second switching elements coupled in a half-bridge configuration. The switching elements are controlled to facilitate resonant operation of the circuit. A circuit path to a load energized by the inverter circuit includes resistive, inductive and capacitive circuit elements coupled in various series and parallel arrangements.
Inverter circuits generally have diodes, known as free wheeling or antiparallel diodes, coupled across terminals of the switching elements such that the diodes are biased into a conduction state when the switching element is biased into its non-conduction state and vice-versa. These diodes become conductive for a period of time during which none of the bridge switching elements are conductive. This time is commonly referred to as dead time. During the dead time, the free wheeling diodes provide a discharge path for energy stored in the resonant inductive and capacitive circuit elements. As known to one of ordinary skill in the art, if the charge stored in the circuit elements is not provided with a discharge path, the energy will resonate in parasitic capacitive and inductive circuit elements. Such resonance will generate high voltages and frequencies that could destroy circuit elements.
While the free wheeling diodes provide a discharge path during the dead time, these diodes do not prevent avalanche current flow through the switching elements. The voltage drop across a conductive free wheeling diode can reverse bias a switching element thereby facilitating avalanche current flow through the switching element. The undesirable avalanche current flow can damage the switching element and may reduce the reliability of the switching element and any circuit which includes the switching element. Avalanche current flow will also slow switching element transitions between conductive and non-conductive states due to the time required for the stored energy from the avalanche current to discharge.
It would, therefore, be desirable to provide a circuit having switching elements that are biased to reduce or eliminate avalanche current flow.
SUMMARY OF THE INVENTION
The present invention provides a circuit that reduces or eliminates avalanche current flow through circuit switching elements. Although the circuit is primarily shown and described as a resonant inverter circuit, it is understood that the circuit has other applications as well.
In one embodiment, a resonant inverter circuit in accordance with the present invention includes first and second switching elements with a first inductive element coupled therebetween. A first freewheeling diode is coupled across the first switching element and a second freewheeling diode is coupled across the second switching element.
A first bias element having an inductive impedance characteristic is coupled to the first switching element and a second bias element having an inductive impedance characteristic is coupled to the second switching element. The first and second bias elements are inductively coupled to the first inductive element such that the bias elements reduce or eliminate avalanche current through a respective switching element.
In operation, each of the first and second switching elements are switched at a duty cycle slightly less than fifty percent. The first switching element is conductive for about one-half of a resonant cycle as current flows in a first direction and the second switching element is conductive for the other half of the resonant cycle as current flows in an opposite direction. If the first and second switching elements are simultaneously conductive, the positive and negative rails of the inverter are shorted together. This is referred to as cross conduction. To prevent cross conduction, there is a period of time known as dead time where the first and second switching elements are non-conductive. During the dead time, one of the first and second freewheeling diodes provides a
-2- discharge signal path to discharge energy stored in the inductive and capacitive circuit elements. The first bias element negates reverse biasing of the first switching element by a voltage drop across the conductive first diode. By preventing reverse biasing of the first switching element, avalanche current flow can be reduced or in some instances eliminated. Similarly, the second bias element prevents or eliminates avalanche current flow through the second switching element as the second diode conducts current.
BRIEF DESCRIPTION OF THE DRAWINGS
The invention will be more fully understood from the following detailed description taken in conjunction with the accompanying drawings, in which: Figure 1 is a circuit diagram of an exemplary circuit in accordance with the present invention;
Figure 2 is a circuit diagram of a part of the circuit of Figure 1 ;
Figure 3 is a further embodiment of a circuit in accordance with the present invention;
Figure 4 is another embodiment of a circuit in accordance with the present invention; and
Figure 5 is a circuit diagram of an exemplary embodiment of a part of the circuit of Figure 4.
DETAILED DESCRIPTION
Referring now to FIGS. 1-3 in which like elements are provided having like reference designations, an exemplary embodiment of a circuit 100, here corresponding to a resonant inverter circuit, in accordance with the present invention is shown. The inverter circuit 100 includes first and second switching elements 101a, 101b here shown as transistor switches Ql ,Q2, coupled in a half-bridge configuration. The first switching element Ql is coupled to a positive rail 102 of the inverter and the second switching element Q2 is coupled to a negative rail 104. Coupled between the first and second switching elements Q1,Q2 are a resonant inductive element LR and a resonant capacitive
-3- element CP. A load 106, such as a fluorescent lamp, is coupled in parallel with the resonant capacitive element CP. The circuit 100 can also include a first bridge capacitor CB1 coupled in between the load 106 and the positive rail 102 and a second bridge capacitor CB2 coupled between the load and the negative rail 104.
The first and second switching elements 101a, b can be formed from bipolar junction transistors (BJTs), field effect transistors (FETs), or other switching elements known to one of ordinary skill in the art. The switching elements 101a, 101b can also be formed from a plurality of switching elements and/or integrated circuits. In an exemplary embodiment, the first switching element Ql is a BJT with a first or collector terminal 108 coupled to the positive rail 102, a second or base terminal 110 coupled to a first control circuit 114 and a third or emitter terminal 112 coupled to a first terminal of a first inductive element LQl. A collector terminal 116 of the second switching element Q2 is coupled to a second terminal of the resonant inductive element LR, a base terminal 118 is coupled to a second control circuit 120 and an emitter terminal 122 is coupled to a second inductive element LQ2. The second inductive element LQ2 is coupled between the emitter terminal 122 of the second switching element Q2 and the negative rail 104. The first and second control circuits 104,106 control the conduction state of the respective first and second switching elements Q1,Q2 to facilitate resonant operation of the inverter circuit 100. Exemplary control circuits for controlling the switching elements Q1,Q2 are disclosed in U.S. Patent Nos. 5, 124,619 (Moisin et al.), 5, 138,234 (Moisin), and 5, 138,236 (Bobel et al.), all incorporated herein by reference.
Coupled across the first switching element Ql is a first diode Dl, commonly referred to as a free wheeling or antiparallel diode. Similarly, a second free wheeling diode D2 is coupled across the second switching element Q2. In the exemplary embodiment shown, the first inductive element LQl is coupled between an anode 124 of the first free wheeling diode Dl and the emitter terminal 112 of the first switching element Ql. A cathode 126 of the first diode Dl is coupled to the collector terminal 108 of the first switching element Ql . The second free-wheeling diode D2 has a cathode 128 coupled to the collector terminal 116 of the second switching element Q2 and an anode 130 coupled to the second inductive element LQ2. The second inductive element LQ2 is coupled between the anode 130 of the second diode D2 and the emitter terminal 1-22 of the second switching element Q2. The anode 130 is also coupled to the negative rail 104 of the inverter.
The first and second inductive elements LQ1,LQ2 are inductively coupled to the resonant inductive element LR. The first inductive element LQl has a polarity indicated by a dot as shown, in accordance with conventional dot notation. Similarly, the second inductive element LQ2 has a polarity as indicated by a dot as shown. As known to one of ordinary skill in the art, the dot indicates a rise in voltage from the unmarked to the marked terminal. For example, current flowing into the dot on a primary side of a transformer has a positive polarity. The first and second inductive elements LQ1,LQ2 reduce or eliminate avalanche current flow from the respective collector terminals
108, 116 to the base terminal 110, 118 by biasing the respective first and second switching elements Q1,Q2, as described below.
In operation, the inverter circuit operates at or near a characteristic resonant frequency of the circuit with the first and second switching elements Q1,Q2 alternately conducting current. It is understood that the switching elements Q1,Q2 have a conductive or ON state in which current flows through the switching element and a non- conductive or OFF state in which state current does not flow through the switching element. An inverter circuit driving a load having resistive, capacitive and inductive impedance characteristics is generally referred to a resonant inverter circuit. As known to one of ordinary skill in the art, the resistive, capacitive and inductive elements, here the load 106, the resonant capacitive element CP and the resonant inductive element LR, determine the resonant frequency for the circuit. During resonant operation of the circuit, a generally sinusoidal current flows to the load 106. The AC load current flows through the resonant elements LR, CP and the load 106 in a first direction during a first part of a resonant cycle and in a second, opposite direction during a second part of the resonant cycle. The first switching element Ql is conductive as the current flows in a direction from the resonant inductive element LR to the load 106 and the second switching element Q2 is conductive as current flows from the load 106 to the resonant inductive element LR. To prevent cross conduction, the first and second switching elements Q1,Q2 should not be biased into their conductive states at the same time. If the first and second switching elements Q1,Q2 are conductive simultaneously, the switches provide a signal path having a relatively low resistance characteristic (e.g. , a short circuit) between the positive and negative rails 102,104. A resultant current could destroy circuit elements. To ensure that cross conduction does not occur as the switching elements Q1,Q2 transition between conduction states, the first and second control circuits Ql ,Q2 provide a period of time, referred to as dead time, where both the first and second switching elements Q1,Q2 are biased into their non-conduction or OFF state. However, when both switching elements Q1,Q2 are biased into their OFF state, energy stored in the inductive and capacitive circuit elements, e.g., LR, CP, can produce one or more parasitic resonant signals having relatively high frequencies and relatively high voltages. Such resonant signals may damage circuit elements exposed thereto. To prevent or reduce the occurrences of the parasitic resonant signals, a dissipation signal path is used to discharge the energy stored in circuit elements such as inductive element LR and capacitive element CP.
The first and second free wheeling diodes D1,D2 provide the dissipation circuit path through which circuit elements discharge stored energy during the dead time when both the first and second switching elements Q1,Q2 are OFF. The order in which the switching elements Q1,Q2 and the diodes D1,D2 are conductive depends upon whether the load is underdamped or overdamped. If the load 106 is purely resistive, i.e., not underdamped or overdamped, the free wheeling diodes D1,D2 do not conduct. If the circuit operates at a frequency below the resonant frequency, i.e. , the load is underdamped, a conduction sequence is: first switching element Ql; first diode Dl; second switching element Q2; and second diode D2. For circuit operation at a frequency above resonance, i.e. , overdamped, the conduction sequence is: first diode Dl; first switching element Ql.; second diode D2; and second switching element Q2.
Looking more closely at circuit operation above resonance and to an exemplary transition from the first switching element Ql switching OFF to the second switching element Q2 switching ON, it can be seen that the second inductive bias element LQ2
-6- reduces or eliminates avalanche current flow from the collector 116 to the base 118 of the second switching element Q2. As the first switching element Ql turns OFF, the second diode D2 turns ON. When the first switching element Ql is turned OFF by the first control circuit 114, the voltage across the first diode Dl increases which causes the voltage across the second diode D2 to concomitantly increase. At about 0.7 Volts (- O.7V with respect to the collector 116 and emitter 122 of Q2), the second diode D2 turns
ON. The voltage drop across diode D2 creates a reverse bias with respect to second switching element Q2.
However, the reverse bias of the second switching element Q2 by diode D2 is counterbalanced by a potential of the second bias element LQ2 so that avalanche current does not flow from the collector 116 to the base 118 of the second switching element Q2.
Avalanche current flows through the collector-base junction of an npn transistor occurs when the collector is at a more negative potential than the emitter. The second bias element LQ2 applies a bias to the emitter 122 of the second switching element Q2 to prevent avalanche current flow by forcing the emitter to a potential that is more negative than the potential of the collector.
FIG. 2 shows the polarities of the bias elements LQ1,LQ2 with respect to the resonant inductive element LR as indicated with conventional dot notation. Voltage polarities are indicated with a " + " for a positive voltage and a "-" for a negative voltage. The respective voltage polarities for the inductive circuit elements LR,LQ1,LQ2 for current flow while Ql is ON are shown without parentheses. As Ql turns OFF, the voltage polarities switch and are shown in parentheses.
The switch in voltage polarity of the second switching element LQ2 provides a negative bias to the emitter 122 of the second switching element Q2. This negative bias offsets the reverse bias applied to the second switching element Q2 by the conductive second diode D2. By maintaining the emitter 122 at a lower voltage potential than the collector 116, avalanche current flow from the collector 116 to the base 118 of the second switching element Q2 is reduced or eliminated.
Similarly, the first bias element LQl provides a negative bias to the emitter 112 of the first switching element Ql when the first diode Dl is conductive prior to the first
-7- switching element Ql transitioning to the ON state. This occurs as the second switching element Q2 turns OFF. Avalanche current flow from the collector 108 of the first switching element Ql to the emitter 110 is prevented by the bias of the emitter 112 by the first bias element LQl.
This circuit arrangement provides a more reliable circuit since the switching elements are not subject to avalanche current flow. The switching elements Q1,Q2 are also more consistent in operation since they are not saturated and unknown times for charge stored in the collector-base junction to discharge are not required. Since energy is not stored in the collector-base junction, the switching element can transition between conduction states more rapidly. Further, the impedance provided by the first and second bias elements limits current flow through the first and second switching elements should cross conduction occur.
FIG. 3 shows a further embodiment of an inverter circuit, and in particular the first and second control circuits 114,120, in accordance with the present invention, wherein like reference designations represent like elements. The first control circuit 114 is coupled to the base 110 of the first switching element Ql and includes a first resistor
Rl coupled between the base and the first bias element LQl . A first capacitor Cl is coupled between the base 110 and emitter 112 of the first switching element. Similarly, the second control circuit 120 includes a second capacitor C2 coupled between the base and emitter terminals 118, 122 of the second switching element Q2. A second resistor R2 is coupled between the base 118 of the second switching element Q2 and the negative rail 104 of the inverter. This arrangement references the base of the switching element Q2 to the negative rail, thus making the circuit less sensitive to parametric variations of the switching element, e.g., transistor.
FIG. 4 is another exemplary embodiment of a circuit 200 providing avalanche current prevention, wherein like reference designation indicate like elements . The circuit
200 shows a part of an inverter circuit including first and second switching elements Ql ,Q2 coupled in a half bridge configuration. The switching elements Ql ,Q2 are shown as npn transistors. The first switching element Ql has a collector terminal 202 coupled
-8- to a positive rail 204 of the inverter, a base terminal 206 coupled to a control circuit 208 and an emitter terminal 210 coupled to a first inductive bias element LQl.
The first inductive bias element LQl has a first terminal 212 coupled to the emitter terminal 210 of the first switching element Ql and a second terminal 214 coupled to a first terminal 216 of a loop inductive element LQl A. A first antiparallel diode Dl is coupled between a second terminal 218 of the loop inductive element LQ1A and the positive rail 204 of the inverter. In an exemplary embodiment, the second terminal 218 of the loop inductive element LQl A is also coupled to a resonant inductive element LR and a collector 220 of the second switching element Q2.
As described above in conjunction with FIGS. 1-3 , the first inductive bias element LQl is effective to reduce or prevent avalanche current from flowing through the first switching element Ql by forcing the emitter terminal 210 to a more negative potential than that of the collector terminal 202 when the first antiparallel diode Dl is conductive. This occurs immediately after the second switching element Q2 turns off but before the first switching element Ql turns on, i.e., the dead time. While the first inductive bias element LQl prevents avalanche current flow, the voltage across this inductive element tends to cause to a current flow through a circuit loop including the first diode Dl and the first switching element Ql . However, the loop inductive bias element LQl A is effective to limit or minimize the current flowing through this circuit loop. Looking to the respective polarities (indicated by conventional dot notation) of the first inductive bias element LQl and the loop inductive bias element
LQl A, it can be seen that these elements are of opposite polarity. The loop inductive bias element LQl A therefore reduces the voltage that appears across the remainder of the circuit loop elements, e.g., the first diode Dl and the first switching element Ql . By reducing this voltage, the amount of current flowing through the Dl/Ql circuit loop is also reduced.
The impedance characteristics of the first inductive bias element LQl as compared with the loop inductive element LQl A can vary. In general, the number of turns of the loop inductive element LQl A is less than or equal to the number of turns of the first
-9- inductive bias element LQl. In one embodiment, the first inductive bias element LQl and the loop inductive element LQl A each have three turns.
FIG. 5 is an exemplary embodiment of the control circuit 208 of FIG. 4. The control circuit includes a collector-base resistor RCB and a base resistor RB coupled in series between the positive rail 204 of the inverter and a point between the first inductive bias element LQl and the loop inductive element LQl A. The base terminal 206 of the first switching element Ql is coupled to a node 207 between the series-coupled resistors RCB,RB. A base-emitter capacitor CBE is coupled between the emitter terminal 210 and the node 207. A base-emitter resistor RBE is also coupled between the emitter terminal 210 and the node 207. The resulting R-C network is effective to control the conduction state of the first switching element Ql during resonant operation of the inverter circuit
200. It is understood that a similar R-C network can control the conduction state of the second switching element Q2.
It is understood that the inverter circuit of the present invention is not limited to the particular embodiments shown. For example, in another embodiment, an inverter can be formed in a full bridge configuration with additional switching elements. Also, the configuration of the resonant inductive and capacitive elements and load can be coupled in various combinations such as parallel loaded (FIG. 1), series-parallel loaded, and various other arrangements known to one skilled in the art.
One of ordinary skill in the art will realize further features and advantages of the invention from the above-described embodiments. Accordingly, the invention is not to be limited by what has been particularly shown and described, except as indicated by the appended claims. All references cited herein are expressly incorporated by reference in their entirety.
What is claimed is:
-10-

Claims

1. A circuit, comprising: a resonant circuit including a first switching element and a resonant inductive element for coupling to a load, the first switching element having a first terminal, a second terminal and a third terminal; and a first inductive bias element inductively coupled to the resonant inductive element, the first bias element being coupled to the first switching element for biasing the first switching element against avalanche current flow.
2. The circuit according to claim 1 , wherein the first bias element is coupled to the third terminal of the first switching element.
3. The circuit according to claim 1 , further including a first current switch element having a first terminal coupled to the first terminal of the first switching element and a second terminal coupled to the first bias element.
4. The circuit according to claim 3, wherein the first current switch element is a diode.
5. The circuit according to claim 1 , wherein the first bias element biases the first switching element against avalanche current flowing from the first terminal to the second terminal of the first switching element.
6. The circuit according to claim 1 , wherein the first switching element is a bipolar junction transistor having collector, base and emitter terminals.
7. The circuit according to claim 6, wherein the first bias element biases the emitter terminal of the first switching element against avalanche current flow from the collector terminal to the base terminal.
8. The circuit according to claim 1 , wherein the circuit is a resonant inverter circuit.
-11-
9. The circuit according to claim 8, wherein the first switching element is coupled to a positive rail of the inverter and further including a second switching element coupled to a negative rail of the inverter and to the first switching element in a half bridge configuration.
10. The circuit according to claim 9, further including a second inductive bias element coupled to the second switching element for biasing the second switching element against avalanche current flow.
11. The circuit according to claim 10, wherein the second bias element is inductively coupled with the resonant inductive element.
12. The circuit according to claim 8, wherein the inverter circuit operates at a frequency greater than a resonant frequency of the inverter circuit.
13. The circuit according to claim 1, further including a second switching element coupled to the first switching element, the second switching element having a first terminal, a second terminal and a third terminal.
14. The circuit according to claim 13, further including a second current switch element coupled across the first and third terminal of the second switching element.
15. The circuit according to claim 14, further including a second bias element coupled to a third terminal of the second switch element.
16. The circuit according to claim 1, further including a first control circuit coupled to the second terminal of the first switching element.
17. The circuit according to claim 16, wherein the first control circuit comprises an RC network.
32-
18. The circuit according to claim 17, wherein the RC network couples the second and third terminals of the first switching element.
19. The circuit according to claim 1, further including a loop inductive element inductively coupled to the first bias element.
20. The circuit according to claim 19, wherein the loop inductive element and the first bias element have opposite polarities.
21. The circuit according to claim 20, wherein the loop inductive element and the first bias element have similar impedance characteristics.
22. The circuit according to claim 5, further including a loop inductive element inductively coupled to the first bias element, the loop inductive element and the first bias element being coupled in series.
23. A resonant inverter circuit, comprising: a first switching element having a first terminal, a second terminal and a third terminal; a second switching element having a first terminal, a second terminal and a third terminal, the second switching element being coupled to the first switching element; a resonant inductive element coupled between the first and second switching elements; a first diode coupled across the first and third terminals of the first switching element; a second diode coupled across the first and third terminals of the second switching element; a first inductive bias element coupled to the third terminal of the first switching element, the first bias element being inductively coupled to the resonant inductive element; and a second inductive bias element coupled to the third terminal of the second
-13- switching element, the second bias element being inductively coupled to the resonant inductive element.
24. The circuit according to claim 23, wherein the first bias element has a polarity with respect to a polarity of the resonant inductive element such that the first bias element biases the first switching element to resist avalanche current flow when the first diode is conductive.
25. The circuit according to claim 24, further including a loop inductive element inductively coupled to the first bias element in opposite polarity, the loop inductive element and the first bias element being coupled in series.
26. The circuit according to claim 25, wherein the loop inductive element is effective to limit current flow through the first diode when the first diode is conductive.
27. A circuit, comprising: a resonant circuit including a first switching element and a resonant inductive element for coupling to a load, the first switching element having a first terminal, a second terminal and a third terminal; a first inductive bias element inductively coupled to the resonant inductive element, the first bias element being coupled to the first switching element for biasing the first switching element against avalanche current flow; and a first loop inductive element inductively coupled to the first bias element, the first loop inductive element being coupled to the first bias element and the resonant inductive element.
28. The circuit according to claim 21 , wherein the first bias element and the first loop inductive element are of opposite polarity.
-14-
29. The circuit according to claim 21, wherein the first bias element and the first loop inductive element have similar impedance characteristics.
30. The circuit according to claim 21, wherein the circuit is a resonant inverter circuit and further includes an antiparallel diode coupled across the first switching element, wherein the loop inductive element is effective to reduce a current flow through the antiparallel diode.
-15-
PCT/US1999/007744 1998-05-06 1999-04-08 Inverter circuit with avalanche current prevention WO1999057801A1 (en)

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EP99915338A EP1092262A1 (en) 1998-05-06 1999-04-08 Inverter circuit with avalanche current prevention
AU33876/99A AU3387699A (en) 1998-05-06 1999-04-08 Inverter circuit with avalanche current prevention
CA002331376A CA2331376A1 (en) 1998-05-06 1999-04-08 Inverter circuit with avalanche current prevention

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US09/073,774 US6091288A (en) 1998-05-06 1998-05-06 Inverter circuit with avalanche current prevention

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Families Citing this family (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6469919B1 (en) * 1999-07-22 2002-10-22 Eni Technology, Inc. Power supplies having protection circuits
US7180758B2 (en) * 1999-07-22 2007-02-20 Mks Instruments, Inc. Class E amplifier with inductive clamp
US6674246B2 (en) 2002-01-23 2004-01-06 Mihail S. Moisin Ballast circuit having enhanced output isolation transformer circuit
US6936977B2 (en) * 2002-01-23 2005-08-30 Mihail S. Moisin Ballast circuit having enhanced output isolation transformer circuit with high power factor
DE10231989B3 (en) * 2002-07-15 2004-04-08 Wurdack, Stefan, Dr. Device for determining surface resistance of a probe, especially a semiconductor wafer, measures conductance with eddy currents and exact position of the wafer
US6861835B2 (en) * 2002-12-03 2005-03-01 Ballard Power Systems Corporation Method and system for non-invasive power transistor die voltage measurement
US7061187B2 (en) * 2003-03-19 2006-06-13 Moisin Mihail S Circuit having clamped global feedback for linear load current
US7099132B2 (en) * 2003-03-19 2006-08-29 Moisin Mihail S Circuit having power management
US6954036B2 (en) * 2003-03-19 2005-10-11 Moisin Mihail S Circuit having global feedback for promoting linear operation
US7642728B2 (en) * 2003-03-19 2010-01-05 Moisin Mihail S Circuit having EMI and current leakage to ground control circuit
US20060238146A1 (en) * 2005-04-25 2006-10-26 Moisin Mihail S Methods and apparatus to enhance operation of fluorescent lamps
US20060261840A1 (en) * 2005-05-18 2006-11-23 Texas Instruments, Inc. System and method for determining channel mobility
US8344801B2 (en) 2010-04-02 2013-01-01 Mks Instruments, Inc. Variable class characteristic amplifier
US8941956B2 (en) * 2011-07-26 2015-01-27 Railpower, Llc Switching ground tether circuit

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4689731A (en) * 1986-08-07 1987-08-25 Honeywell Inc. MOSFET inverter gate drive circuit
EP0291120A2 (en) * 1987-05-11 1988-11-17 Philips Electronics North America Corporation A regulated high frequency power supply
WO1990007820A1 (en) * 1989-01-09 1990-07-12 Sundstrand Corporation Inverter switch current sensor
SU1737683A1 (en) * 1989-10-03 1992-05-30 Научно-исследовательский институт газоразрядных приборов Dc voltage converter

Family Cites Families (88)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3808481A (en) * 1972-04-14 1974-04-30 Electric Fuel Propulsion Corp Commutating circuit for electrical vehicle
CA1034195A (en) * 1975-01-22 1978-07-04 Thomas A. Young Multiphase to single phase and frequency converter system
US4164785A (en) * 1976-09-27 1979-08-14 Tenna Power Corporation Multiphase to single phase and frequency converter system
US5481160A (en) * 1978-03-20 1996-01-02 Nilssen; Ole K. Electronic ballast with FET bridge inverter
US4270164A (en) * 1979-02-28 1981-05-26 Contraves Goerz Corporation Short circuit protection for switching type power processors
US4423363A (en) * 1981-07-27 1983-12-27 General Electric Company Electrical braking transitioning control
US4415839A (en) * 1981-11-23 1983-11-15 Lesea Ronald A Electronic ballast for gaseous discharge lamps
FR2518333B1 (en) * 1981-12-14 1986-04-04 Aerospatiale DEVICE FOR SWITCHING A CONTINUOUS ELECTRIC VOLTAGE SOURCE PROVIDED WITH AT LEAST ONE CONTROLLED SWITCH AND SWITCHING AID CIRCUIT FOR SUCH A DEVICE
NL8201631A (en) * 1982-04-20 1983-11-16 Philips Nv DC AC CONVERTER FOR IGNITION AND AC POWERING A GAS AND / OR VAPOR DISCHARGE LAMP.
US4675576A (en) * 1985-04-05 1987-06-23 Nilssen Ole K High-reliability high-efficiency electronic ballast
US4507698A (en) * 1983-04-04 1985-03-26 Nilssen Ole K Inverter-type ballast with ground-fault protection
US5216332A (en) * 1982-08-25 1993-06-01 Nilssen Ole K Magnetic-electronic ballast for fluorescent lamps
US4608958A (en) * 1982-09-22 1986-09-02 Nippon Soken, Inc. Load reactance element driving device
US4480298A (en) * 1983-01-25 1984-10-30 Westinghouse Electric Corp. Multiple output DC-to-DC voltage converter apparatus
US4618810A (en) * 1983-02-04 1986-10-21 Emerson Electric Company Variable speed AC motor control system
US4572988A (en) * 1983-08-22 1986-02-25 Industrial Design Associates, (Ida) High frequency ballast circuit
NL8402351A (en) * 1984-07-26 1986-02-17 Philips Nv DC AC CONVERTER FOR POWERING A METAL VAPOR DISCHARGE TUBE.
US4624334A (en) * 1984-08-30 1986-11-25 Eaton Corporation Electric power assisted steering system
US4682083A (en) * 1984-10-29 1987-07-21 General Electric Company Fluorescent lamp dimming adaptor kit
NL8500155A (en) * 1985-01-22 1986-08-18 Philips Nv ELECTRICAL DEVICE FOR CONTROLLING THE LIGHT OF AT LEAST AT LEAST A DISCHARGE LAMP.
US5027032A (en) * 1985-10-18 1991-06-25 Nilssen Ole K Electronically controlled magnetic fluorescent lamp ballast
US5256939A (en) * 1985-10-24 1993-10-26 Nilssen Ole K Magnetic electronic fluorescent lamp ballast
US5004955A (en) * 1986-02-18 1991-04-02 Nilssen Ole K Electronic ballast with shock protection feature
US4783728A (en) * 1986-04-29 1988-11-08 Modular Power Corp. Modular power supply with PLL control
JPS632464A (en) * 1986-06-20 1988-01-07 Matsushita Graphic Commun Syst Inc Coupling output circuit for variable length data
US4818917A (en) * 1986-07-07 1989-04-04 Vest Gary W Fluorescent lighting ballast with electronic assist
US4991051A (en) * 1986-09-12 1991-02-05 Northern Telecom Limited Protection arrangements for communications lines
JPS63140694A (en) * 1986-12-01 1988-06-13 Janome Sewing Mach Co Ltd Stepping motor driving device
JP2711315B2 (en) * 1987-05-07 1998-02-10 ニシム電子工業株式会社 Switching power supply
US4870327A (en) * 1987-07-27 1989-09-26 Avtech Corporation High frequency, electronic fluorescent lamp ballast
US4866586A (en) * 1988-06-13 1989-09-12 Westinghouse Electric Corp. Shoot-through resistant DC/DC power converter
US4899382A (en) * 1988-06-15 1990-02-06 Siemens Transmission Systems, Inc. Telephone circuit using DC blocked transformer and negative impedance technique
US4864486A (en) * 1988-07-29 1989-09-05 International Business Machines Corporation Plank and frame transformer
US4952853A (en) * 1988-08-24 1990-08-28 General Electric Company Method and apparatus for sensing direct current of one polarity in a conductor and electronically commutated motor control responsive to sensed motor current
US5014305A (en) * 1989-03-16 1991-05-07 Northern Telecom Limited Line interface circuit
US5003231A (en) * 1989-04-12 1991-03-26 Peroxidation Systems, Inc. Adaptive resonant ballast for discharge lamps
US5052039A (en) * 1990-01-16 1991-09-24 Northern Telecom Limited Line interface circuit
DE4010435A1 (en) * 1990-03-31 1991-10-02 Trilux Lenze Gmbh & Co Kg Mains connection device for fluorescent lamp - has inverse regulator for prodn. of constant operating voltage, and electronic switch in series branch to load in series with diode
JP2658506B2 (en) * 1990-06-06 1997-09-30 三菱電機株式会社 Rare gas discharge fluorescent lamp device
US5173643A (en) * 1990-06-25 1992-12-22 Lutron Electronics Co., Inc. Circuit for dimming compact fluorescent lamps
US5081401A (en) * 1990-09-10 1992-01-14 Motorola, Inc. Driver circuit for a plurality of gas discharge lamps
DE4032664A1 (en) * 1990-10-15 1992-04-16 Horst Erzmoneit Operating circuitry for low pressure gas discharge lamp - includes PTC resistance in parallel with choke coil for reduced power warm starting
US5138233A (en) * 1991-03-07 1992-08-11 Motorola, Inc. Driver circuit for a plurality of gas discharge lamps
US5291382A (en) * 1991-04-10 1994-03-01 Lambda Electronics Inc. Pulse width modulated DC/DC converter with reduced ripple current coponent stress and zero voltage switching capability
US5315533A (en) * 1991-05-17 1994-05-24 Best Power Technology, Inc. Back-up uninterruptible power system
US5138234A (en) * 1991-05-28 1992-08-11 Motorola, Inc. Circuit for driving a gas discharge lamp load
US5148087A (en) * 1991-05-28 1992-09-15 Motorola, Inc. Circuit for driving a gas discharge lamp load
US5144195B1 (en) * 1991-05-28 1995-01-03 Motorola Lighting Inc Circuit for driving at least one gas discharge lamp
US5124619A (en) * 1991-05-28 1992-06-23 Motorola, Inc. Circuit for driving a gas discharge lamp load
US5138236B1 (en) * 1991-05-28 1996-11-26 Motorola Lighting Inc Circuit for driving a gas discharge lamp load
DE4120649A1 (en) * 1991-06-22 1992-12-24 Vossloh Schwabe Gmbh OVERVOLTAGE PROTECTED BALLAST
US5097183A (en) * 1991-06-25 1992-03-17 Led Corporation N.V. Master-slave half-bridge DC-to-AC switchmode power converter
US5177408A (en) * 1991-07-19 1993-01-05 Magnetek Triad Startup circuit for electronic ballasts for instant-start lamps
US5223767A (en) * 1991-11-22 1993-06-29 U.S. Philips Corporation Low harmonic compact fluorescent lamp ballast
US5191263A (en) * 1992-03-04 1993-03-02 Motorola Lighting, Inc. Ballast circuit utilizing a boost to heat lamp filaments and to strike the lamps
US5220247A (en) * 1992-03-31 1993-06-15 Moisin Mihail S Circuit for driving a gas discharge lamp load
JP3226599B2 (en) * 1992-05-19 2001-11-05 東芝アイティー・コントロールシステム株式会社 Battery car control method and device
US5309066A (en) * 1992-05-29 1994-05-03 Jorck & Larsen A/S Solid state ballast for fluorescent lamps
US5334912A (en) * 1992-08-24 1994-08-02 Usi Lighting, Inc. Ground fault detector and associated logic for an electronic ballast
US5432817A (en) * 1992-09-28 1995-07-11 Corporation Chrysler Vehicle communications network transceiver, ground translation circuit therefor
US5332951A (en) * 1992-10-30 1994-07-26 Motorola Lighting, Inc. Circuit for driving gas discharge lamps having protection against diode operation of the lamps
US5399943A (en) * 1992-12-24 1995-03-21 Micro-Technology, Inc.-Wisconsin Power supply circuit for a discharge lamp
US5434477A (en) * 1993-03-22 1995-07-18 Motorola Lighting, Inc. Circuit for powering a fluorescent lamp having a transistor common to both inverter and the boost converter and method for operating such a circuit
US5390231A (en) * 1993-04-01 1995-02-14 Northern Telecom Limited Protection and recovery of telephone line interface circuits
US5444333A (en) * 1993-05-26 1995-08-22 Lights Of America, Inc. Electronic ballast circuit for a fluorescent light
US5434480A (en) * 1993-10-12 1995-07-18 Bobel; Andrzej A. Electronic device for powering a gas discharge road from a low frequency source
US5563479A (en) * 1993-10-29 1996-10-08 Aisin Seiki Kabushiki Kaisha Power supply apparatus for electric vehicle
US5416388A (en) * 1993-12-09 1995-05-16 Motorola Lighting, Inc. Electronic ballast with two transistors and two transformers
US5583402A (en) * 1994-01-31 1996-12-10 Magnetek, Inc. Symmetry control circuit and method
JP3153408B2 (en) * 1994-03-10 2001-04-09 株式会社日立製作所 Series multiplex power converter
US5686799A (en) * 1994-03-25 1997-11-11 Pacific Scientific Company Ballast circuit for compact fluorescent lamp
JP3193827B2 (en) * 1994-04-28 2001-07-30 三菱電機株式会社 Semiconductor power module and power converter
US5504398A (en) * 1994-06-10 1996-04-02 Beacon Light Products, Inc. Dimming controller for a fluorescent lamp
DE4421736C2 (en) * 1994-06-22 1998-06-18 Wolfgang Nuetzel Controllable lighting system
US5495404A (en) * 1994-07-29 1996-02-27 Motorola, Inc. Multi-resonant inverter
US5574335A (en) * 1994-08-02 1996-11-12 Osram Sylvania Inc. Ballast containing protection circuit for detecting rectification of arc discharge lamp
US5515433A (en) * 1994-08-30 1996-05-07 Reltec Corporation Resistance forward telephone line feed circuit
US5608295A (en) * 1994-09-02 1997-03-04 Valmont Industries, Inc. Cost effective high performance circuit for driving a gas discharge lamp load
US5691606A (en) * 1994-09-30 1997-11-25 Pacific Scientific Company Ballast circuit for fluorescent lamp
US5579197A (en) * 1995-01-24 1996-11-26 Best Power Technology, Incorporated Backup power system and method
US5493180A (en) * 1995-03-31 1996-02-20 Energy Savings, Inc., A Delaware Corporation Lamp protective, electronic ballast
US5684683A (en) * 1996-02-09 1997-11-04 Wisconsin Alumni Research Foundation DC-to-DC power conversion with high current output
US5767657A (en) * 1996-03-26 1998-06-16 Motorola, Inc. Battery charger having a battery discharge prevention circuit
DE19612170A1 (en) * 1996-03-27 1997-10-02 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating electric lamps and operating methods for electric lamps
DE19613149A1 (en) * 1996-04-03 1997-10-09 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating electric lamps
US5793127A (en) * 1996-08-02 1998-08-11 Motorola Inc. Inductive load driver circuit with shared flyback protection
US5866993A (en) * 1996-11-14 1999-02-02 Pacific Scientific Company Three-way dimming ballast circuit with passive power factor correction
US5798617A (en) * 1996-12-18 1998-08-25 Pacific Scientific Company Magnetic feedback ballast circuit for fluorescent lamp

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4689731A (en) * 1986-08-07 1987-08-25 Honeywell Inc. MOSFET inverter gate drive circuit
EP0291120A2 (en) * 1987-05-11 1988-11-17 Philips Electronics North America Corporation A regulated high frequency power supply
WO1990007820A1 (en) * 1989-01-09 1990-07-12 Sundstrand Corporation Inverter switch current sensor
SU1737683A1 (en) * 1989-10-03 1992-05-30 Научно-исследовательский институт газоразрядных приборов Dc voltage converter

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
SOVIET PATENTS ABSTRACTS Section EI Week 9318, Derwent World Patents Index; Class U24, AN 93-1510782900559, XP002900559 *

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US6091288A (en) 2000-07-18
CA2331376A1 (en) 1999-11-11
AU3387699A (en) 1999-11-23
EP1092262A1 (en) 2001-04-18

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