EP1227707A2 - Mikrocontroller, Schaltnetzteil und Vorschaltgerät zum Betrieb mindestens einer elektrischen Lampe - Google Patents
Mikrocontroller, Schaltnetzteil und Vorschaltgerät zum Betrieb mindestens einer elektrischen Lampe Download PDFInfo
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- EP1227707A2 EP1227707A2 EP01129890A EP01129890A EP1227707A2 EP 1227707 A2 EP1227707 A2 EP 1227707A2 EP 01129890 A EP01129890 A EP 01129890A EP 01129890 A EP01129890 A EP 01129890A EP 1227707 A2 EP1227707 A2 EP 1227707A2
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- European Patent Office
- Prior art keywords
- microcontroller
- current
- charge
- charging
- discharging
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/36—Controlling
- H05B41/38—Controlling the intensity of light
- H05B41/39—Controlling the intensity of light continuously
- H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
- H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
Definitions
- the invention relates to a microcontroller according to the preamble of the claim 1, a switching power supply according to claim 10, a ballast for at least one electric lamp according to the preamble of claim 11 and a method for operating at least one electric lamp according to the Preamble of claim 25.
- the invention relates to a microcontroller that is used to control the Switching transistors of a switching power supply, preferably a switching power supply is provided for the operation of electric lamps.
- a switching power supply is provided for the operation of electric lamps.
- Inverters in particular half-bridge, full-bridge and push-pull inverters, as well as step-up converters and step-down converters.
- Modern electronic ballasts usually have an inverter for operating electric lamps to generate a high-frequency alternating current for lamp operation and often also a step-up converter as a DC voltage supply for the Inverter on.
- the control of the switching transistors of the inverter and the step-up converter is carried out by means of driver circuits which are considered to be in analog technology executed integrated circuits are formed.
- modern electronic ballasts for electric lamps also a microcontroller, usually for communication with one outside the ballast arranged control unit and for evaluating the control commands of this control unit for lamp operation and for monitoring lamp operation.
- the European patent application EP 0 708 579 A1 discloses a circuit arrangement for operating a high-pressure discharge lamp on an inverter, whose switching transistors by means of a microcontroller and a downstream one integrated driver circuit with pulse width modulated control signals become.
- the pulse width modulated control signals are generated with the help of the Microcontrollers implemented auto reload timer generated. Acting in principle it is a counter with the working clock frequency of the microcontroller is working. During the counting process, reaching a reference value and the Overflow of the counter monitored.
- the output of the auto reload timer is on the Logic level "High” and during the period that the counter starts counting the output lies from the reference value to the counter overflow of the auto reload timer at logic level "Low”. That way, with With the help of the microcontroller, pulse-width-modulated control signals for the inverter generated to be in a small frequency range with a comparatively low one Number of discrete frequencies a lamp operation with a frequency-modulated To allow tension.
- Another object of the invention is to provide a microcontroller Switching power supply with improved control of the switching means of the switching power supply provide.
- the device for alternately loading and unloading a charge storage device and their control means make it possible to alternate in a charge storage device carry out controlled loading and unloading and with the help the evaluation means the time periods for the partial loading or Unloading the cargo storage are needed, evaluate and depending of which a pulse width modulation control signal and / or frequency control signal produce. Even if the microcontroller according to the invention only has a low operating clock frequency possesses a fine-tuned pulse width modulation control and / or frequency control of a switching power supply can be implemented because the device for alternately loading and unloading a charge storage works independently of the microcontroller's operating frequency.
- the device advantageously comprises alternating loading and unloading a charge storage a controllable current source for loading the Charge storage with an adjustable charging current and a controllable Current sink for loading the charge storage device with an adjustable one Discharge.
- the individual loading and unloading processes can be controlled independently.
- the controllable Current source and current sink in a known manner using semiconductor technology manufacture and integrate into the microcontroller.
- the controllable current source and the controllable current sink are such trained that their settings with respect to a reference current level each can be varied with a resolution of at least 8 bits.
- the reference current level for the charging and discharging current is advantageously with the help of a ohmic resistance.
- control means for the device for As control means for the device for alternating loading and unloading Charge memory is advantageously provided at least one read-write memory.
- the content of the random access memory can be continuous, for example be program controlled, updated and used to control the device for alternating Loading and unloading a charge storage can be read.
- the tax revenue advantageously comprise a switching means for switching the device for alternately loading and unloading a load storage from the store to discharge the charge storage when a first voltage value is reached and to switch the device for alternating loading and unloading Charge storage from unloading to loading the charge storage when reaching a second, lower voltage value is used.
- the switching means Device for alternately loading and unloading a charge storage easily forced to alternate loading and unloading operations, so that the charge state of the charge storage is subject to constant oscillation is used to generate frequency control signals and / or pulse width modulation control signals is evaluable.
- the first or the second voltage value are advantageously adjustable by means of a read-write memory. Thereby can program-controlled the aforementioned oscillation of the charge state of the charge store to be influenced.
- the microcontroller according to the invention advantageously has a frequency divider or a pulse divider, which serves to switch the Device for alternately loading and unloading a charge storage device from Discharge to load or from load to discharge to detect and the input signal in signals for alternating control of alternating switching devices of the switching power supply.
- a frequency divider or a pulse divider can the oscillation of the state of charge of the charge storage to generate Frequency control signals and / or pulse width modulation control signals for the Switching means of a switching power supply with alternating switching means evaluated become.
- the microcontroller according to the invention also advantageously has interfaces for recording external signals or data and has a device for Evaluation of the external signals or data and for program-controlled determination of control values for controlling the device for alternating loading and Unload a charge store. This can create a control loop for the oscillation the state of charge of the charge storage as a function of external operating parameters and the control values derived from them.
- the switching power supply according to the invention is characterized by a microcontroller one or more of claims 1 to 9.
- the corresponding Control signals are sent directly from the microcontroller or, if necessary, via driver circuits passed on to the control electrodes of the switching transistors of the switching power supply. As mentioned above, these control signals are independent from the working clock frequency of the microcontroller.
- the device for alternately loading and unloading a charge store, the charge storage and the control means for the device for alternating Charging and discharging a charge storage form an oscillator that is independent from the working clock frequency of the microcontroller works.
- the state of charge oscillations of the charge storage are generated using the evaluation means of frequency control signals and / or pulse width modulation control signals evaluated for the inverter.
- ballast according to the invention it is possible with the help of a relatively simple and inexpensive microcontroller all essential control functions of a modern, dimmable ballast realize.
- these are the power factor correction, the control of the Inverter, the control of the lamp electrode heating, the regulation of the Load circuit, the brightness control of the lamps and the monitoring of lamp operation.
- Ballast according to the invention with comparatively few additional components out.
- Most functions are in the ballast according to the invention taken over by the microcontroller. It is particularly easy to do with the invention Ballast, for example, the end-of-life monitoring of Realize the lamp very well in the ballasts according to the prior art is complex and expensive.
- the device has for alternately controlling the switching means of the inverter for pulse width modulation control and / or frequency control advantageously a frequency divider or a pulse divider on its input the switching of the device for alternately loading and unloading a charge store from unloading to loading or from loading to unloading the cargo storage detects and the input signal in signals for alternating control divides the switching means of the inverter.
- the inventive has Ballast advantageously one with a controllable switching means equipped heating device and the microcontroller has a comparator on the state of charge of the load memory with a reference value for the Lamp electrode heating compares and for generating a control signal Pulse width modulation of the controllable switching means of the heating device is used.
- the reference value for the lamp electrode heater can advantageously be set by means of a read-write memory, around the heating current for the lamp electrodes to the different operating states to be able to adapt the lamp.
- the microcontroller also advantageously has Synchronization means for synchronizing the controllable switching means the heating device with a switching means of the inverter. Thereby the control of the switching means of the heating device is simplified. Moreover this has a positive influence on the vibration behavior of the inverter.
- the DC voltage supply circuit has of the inverter advantageously a step-up converter for power factor correction and / or to achieve a mains current draw that is as sinusoidal as possible on, and the microcontroller is connected to a second device for alternating loading and unloading of a second charge storage and with a second Control means for this second device for controlling the loading and / or Unloading operations.
- the second device for alternate charging and discharging a charge store, the second charge store and the second Control means for this second device form a second oscillator, which also works independently of the microcontroller's operating frequency.
- the microcontroller is also equipped with second evaluation tools that are used to the oscillations of the state of charge of the second charge storage for generation of pulse width modulation control signals and / or frequency control signals evaluate for the controllable switching means of the step-up converter. In particular, be for this, that for reloading the second charge store between different ones Charges required time periods evaluated.
- the microcontroller also takes over the control of the step-up converter.
- the second evaluation means advantageously have a first Comparator for comparing the state of charge of the second charge store with one first voltage value and a second comparator for comparing the state of charge of the second charge storage device with a second, lower voltage value on, and the second control means advantageously have switching means which for switching the second device for alternating loading and unloading of a charge store from store to discharge of the second charge store Reaching the first voltage value and switching the second device for alternately loading and unloading a load storage from unloading to Charging the second charge storage when the second, lower voltage value is reached serve.
- the first or second voltage value is advantageously means a read-write memory adjustable. This allows the first or second Voltage value, for example by means of a program executed by the microcontroller, be changed and to control the second device for alternating Loading and unloading a charge storage can be saved.
- the two devices for alternately loading and unloading a charge storage device each advantageously have a controllable current source for charging the charge storage or the second charge storage with an adjustable Charging current and a controllable current sink to act on the Charge storage or the second charge storage with an adjustable discharge current on.
- the controllable current sources and current sinks can be known Manufacture way using semiconductor technology and in the microcontroller integrate.
- the two device for alternately loading and unloading one Charge storage can thus be part of the microcontroller using simple means getting produced.
- To a fine gradation of the frequency control signals or to ensure the pulse width modulation control signals are the settings the controllable current sources and current sinks with respect to a reference current level each variable with a resolution of at least 8 bits.
- the aforementioned Reference current level for the charging current and the discharging current is advantageously can be specified using an ohmic resistor. This makes it possible to Control of the inverter by appropriate dimensioning of the ohmic Resistance to adapt to different mains voltages. To save components, preferably, only a single ohmic resistance is the default the same reference current level for the charge and discharge currents of the two Charge storage used.
- the microcontroller of the ballast according to the invention advantageously has at least one status bit that can be set and reset, via which at least one controllable switching means of the inverter can be activated and deactivated.
- This status bit can be used to simply switch off the inverter implemented in the event of a defective lamp or end-of-life monitoring of the lamp become.
- the controllable switching means of the step-up converter can of course also be used and thus the power supply to the inverter using the status bit can be deactivated in order to easily switch off the ballast to realize.
- the microcontroller advantageously has one or several more settable and resettable status bits to control the pulse width modulation of the step-up converter or the inverter either off or on to be able to switch on. This makes it possible to switch the controllable switching means Step-up converter and the inverter optionally only with frequency control signals or pulse width modulation control signals or with frequency control signals and pulse width modulation control signals.
- the microcontroller of the ballast according to the invention is advantageous with interfaces for recording operating parameters of the step-up converter or of the inverter or the at least one electric lamp to the operating parameters by means of a program-controlled device of the microcontroller evaluate and control values for the control of the devices for alternating Load and unload a charge store or generate the reference value for lamp electrode heating or the first or second reference value for the control of the step-up converter.
- the Microcontroller with interfaces for recording at least one operating parameter of the step-up converter, the inverter and the load circuit or at least provided an electric lamp. This allows control loops for the Booster, the inverter and the load circuit with the lamp built become.
- the ballast according to the invention advantageously has connections and means for communication with an externally arranged control device, which in turn are coupled to interfaces of the microcontroller.
- the inventive method for operating at least one electrical Lamp on a ballast that has an inverter with a a microcontroller containing control circuit for the switching means of the inverter and at least one load circuit coupled to the inverter with connections for which has at least one lamp is characterized according to the invention in that with the help of the microcontroller, a charge storage alternating with a charging current and a discharge current is applied, and the duration of the alternating Charging and discharging processes of the charge storage is evaluated and dependent thereof a frequency control signal and / or a pulse width modulation control signal generated for alternating control of the switching means of the inverter becomes.
- the method according to the invention makes it possible, regardless of the operating clock frequency the microcontroller with the help of the microcontroller control signals Frequency control and / or to generate pulse width modulation of the inverter. This enables a comparatively inexpensive microcontroller that means a microcontroller with a low operating clock frequency, in the invention Ballast for realizing all essential control functions be used.
- a frequency divider or a pulse divider used to switch the Device for alternately loading and unloading a load storage from Unloading to load the cargo storage or from loading to unloading the cargo storage detected.
- the method according to the invention also enables the lamp electrodes to be heated, by the heating current for the lamp electrodes by means of a controllable Switching means is regulated.
- the signals are advantageously pulse-width modulated Control of the controllable switching means of the heating device with the help a comparator that generates the state of charge of the charge storage with a Reference value for lamp electrode heating is compared. That way you can both for the switching means of the inverter and for the controllable switching means the heating device frequency control signals and / or pulse width modulation control signals generated by the duration of the charging and discharging of the Charge storage is evaluated.
- the reference value for the lamp electrode heater is advantageously dependent on the desired heating output set and stored in a read-write memory of the microcontroller.
- the heating power can thus be set in a program-controlled manner using the microcontroller become.
- the controllable switching means for regulating the heating current advantageously switched on synchronously with a switching means of the inverter. This simplifies the control of the controllable switching means the heater.
- the duty cycle of the controllable switching means for regulation the heating current is preferably less than or equal to the duty cycle of the corresponding one Switching means of the inverter.
- the DC voltage supply of the inverter is made with the help of a step-up converter regulated to a power factor correction and / or a sinusoidal Ensure mains current drain.
- the pulse width modulation control signals are advantageously and / or the frequency control signals for the controllable Switching means of the step-up converter also generated with the help of the microcontroller, by reloading a second charge store between different charge states and the time periods for reloading the second charge storage Generation of the pulse width modulation control signals and / or the frequency control signals be evaluated for the controllable switching means of the step-up converter.
- the same microcontroller that is used to control the inverter can also be used to control the step-up converter.
- Reloading the second charge storage can be easily by means of two comparators can be detected and evaluated by the first comparator the state of charge of the second charge storage device with a first voltage value and the second comparator the state of charge of the second charge storage with a second, lower Compares voltage value.
- the first voltage value is reached, the Charging process ended and the unloading process of the second charge storage started, while the discharge process when the second, lower voltage value is reached ended and the charging process of the second charge store started again becomes.
- the first or second voltage value are advantageously determined using a Read-write memory set. This allows the corresponding voltage value can be varied programmatically.
- FIGs 1 and 2 is the circuit arrangement of the preferred embodiment of the ballast according to the invention shown schematically. Because of The size of the circuit arrangement had to be shown on two sheets. At the connection points labeled J10 to J26 are the two in the figures 1 and 2 shown halves of the circuit arrangement linked together.
- This ballast is a so-called electronic ballast for operating fluorescent lamps.
- the ballast has two mains voltage connections J1, J2 to which one of the capacitor C1 and the Transformer L1 existing filter circuit for radio interference suppression of the ballast connected.
- This filter circuit is connected to a bridge rectifier, which is formed by four rectifier diodes D1, D2, D3 and D4.
- the Bridge rectifier D1-D4 is followed by capacitor C2, which provides the DC voltage output of the bridge rectifier D1-D4.
- To capacitor C2 is a step-up converter connected to the field effect transistor V1, the choke L2, the diode D5 and the resistor R13 comprises.
- the on the capacitor C2 DC voltage is used as supply voltage for the step-up converter.
- the gate electrode of transistor V1 is connected to pin 4 of the resistor R4 Microcontroller MC connected, which takes over the control of the transistor V1.
- the voltage output of the step-up converter is from the intermediate circuit capacitor C3 formed.
- the voltage across the intermediate circuit capacitor C3 is determined by means of the Voltage divider resistors R2, R5 monitored on pin 21 of the microcontroller MC.
- the voltage at the capacitor is also used to control the transistor V1 C2 using the voltage divider resistors R1, R18 on pin 20 of the Microcontroller MC detected.
- a smoothed DC voltage is supplied to the intermediate circuit capacitor C3 for supply of the downstream half-bridge inverter.
- the half-bridge inverter consists essentially of field effect transistors V2, V3, the trapezoidal capacitors C10, C11, the inductor L4, the coupling capacitors C15, C16 and the ignition capacitor C12.
- At the center tap between the two Transistors V2, V3 of the inverter is connected to a load circuit, which Choke L4, the ignition capacitor C12, the connections X1 to X8 for the electrode coils E1, E2 and E3, E4 of the two fluorescent lamps LP1 connected in parallel, LP2, the transformer L5 and the coupling capacitors C15, C16.
- the Ignition capacitor C12 is connected in parallel to both lamps LP1, LP2.
- the coupling capacitors C15, C16 are each arranged in series with one of the lamps LP1, LP2.
- the transformer L5 is used to symmetrize the currents in the lamp circuits.
- one of the transformer windings is in each case one of the lamp circuits, that is, in series with one of the lamps LP1, LP2 arranged.
- the two lamp circuits are at connection X8 and at two connections of the coupling capacitors connected to the internal circuit GRD C15, C16 merged again.
- the gate electrodes of the Transistors V2, V3 are through resistors R6 and R7 from the microcontroller MC controlled by means of the IC integrated circuit, which is essentially only driver circuits for the control of the inverter transistors and Has circuits for generating auxiliary voltages for the microcontroller MC.
- the half-bridge inverter generates in the load circuit for lamps LP1, LP2 a high frequency current with a frequency between about 30kHz and 100 kHz. After ignition of the gas discharge in the lamps LP1, LP2 flow in two lamp circuits via connection X8, the discharge path of the Lamp LP1 or LP2, connection X5 or X7 and over the coupling capacitors C16 or C15 high-frequency lamp currents.
- the inductor L4 and the ignition capacitor C12 are designed as a series resonance circuit.
- the one for igniting the gas discharge The ignition voltage required in the fluorescent lamps is determined using the method the resonance increase at the ignition capacitor C12 provided by during the ignition phase, the switching frequency of the transistors V2, V3 of the half-bridge inverter approximated the resonance frequency of the series resonance circuit becomes.
- the center tap between the inductor L4 and the ignition capacitor C12 is through the capacitor C22, the resistor R24 and the polarized in the forward direction Diode D12 connected to pin 18 of the microcontroller MC.
- pin 18 is by means of resistors R24, R25, diodes D12, D13 and capacitors C22, C23 monitors a half-wave of the AC component of the load current. The other half-wave of the AC component of the current flowing in the load circuit is clamped to the internal ground potential GRD by the diode D13.
- Pin 19 of microcontroller MC is connected to the source electrode via resistor R27 of the transistor V3 and connected to the capacitor C24 circuit-internal ground potential GRD coupled.
- the resistor R9 connects the Source electrode of transistor V3 with the internal circuit potential GRD. The current through transistor V3 is monitored at pin 19.
- the ballast also has a heating device for the electrodes E1-E4 two fluorescent lamps on the center tap between the two field effect transistors V2, V3 of the half-bridge inverter is connected.
- This Heater consists essentially of the field effect transistor V4 and Transformer L3.
- the primary winding of the transformer L3 is on the one hand with the Center tap between the transistors V2, V3 and on the other hand with the drain connection of the transistor V4 and in the forward DC direction via the diode D8 connected to the positive pole of the intermediate circuit capacitor C3.
- the source electrode of transistor V4 is connected via resistor R17 to the circuit Ground potential connected to GRD.
- the three secondary windings of the transformer L3 are, together with lamps LP1, LP2, together with one Rectifier diode D9 or D10 or D11 in a closed circuit for Heating the electrode filaments E1 and E3 or the electrode filament E2 or E4 arranged.
- the heating current in the three with the secondary windings of the transformer L3 equipped heating circuits is regulated by the switching clock of the transistor V4.
- its gate electrode is over resistor R26 connected to pin 10 of microcontroller MC.
- the heater serves on the one hand to preheat the electrode coils E1-E4 before the Gas discharge is ignited in the lamps LP1, LP2, and on the other hand for heating the electrode filaments E1-E4 during the dimming operation of the lamps LP1, LP2.
- the heating current that is, the current through the primary winding of the transformer L3 and the transistor V4 is connected to pin 17 with the aid of the RC element R23, C18 of the microcontroller MC monitors.
- pin 17 is over the Resistor R23 connected to the source of transistor V4.
- Two more DC paths are using resistor R11 or R12 and the diodes D10 or D11 and the resistors R16, R20 or R15, R21 implemented to monitor the electrode coils E2 and E4.
- a break of the Electrode coil E2 or E4 is over the corresponding winding of the transformer L5 and resistor R16 or R15 on pin 16 or 15 from the microcontroller MC detected.
- Pins 15, 16 of the microcontroller MC are also used also by means of the voltage divider resistors R15, R21 or R16, R20 Current through the lamp LP1 or LP2 or the voltage drop across the coupling capacitor C15 or C16 monitors the end of lamp life To detect LP1 or LP2 occurring rectification effect of the lamp LP1 or LP2.
- the ballast also has a communication device DS for communication with an external control device (not shown).
- This facility DS has two connectors J3, J4, which are connected to the external control device are connectable.
- the connections J3, J4 are used to receive digital or analog Control signals from the external control device and for sending information, for example, about the operating state of the lamps from the ballast to the external control device.
- a bidirectional is via the connections J3, J4 Connection to the external control device possible.
- An exit from Communication device DS is with the circuit internal ground potential GRD connected.
- Pin 6 of the MC microcontroller is used to transmit data to the external control unit is connected to the input of the communication device DS and pin 5 of the microcontroller MC is for reception and evaluation of control commands from the external control device to the output of the Communication device DS connected.
- the integrated circuit IC contains driver circuits for the transistors V2, V3, in particular a bootstrap circuit for the transistor V2 and level shift circuits for controlling the transistors V2, V3.
- the capacitor C9 and the Pins 1, 2, 3 and 14 of the integrated circuit IC are these driver circuits assigned to transistors V2, V3.
- the control signals for regulating the switching cycle of the transistors V2, V3 or for frequency control of the half-bridge inverter are generated by the microcontroller MC and via pin 24 or 23 the pin 9 or 10 of the integrated circuit IC supplied.
- pin 13 of the integrated circuit IC with the source connection of transistor V3 connects, and capacitor C8, through which the pin 13 of the integrated circuit IC is coupled to the ground potential GRD realized a detector that the current load of the transistors V2, V3 is too high prevented.
- Pin 5 of the integrated circuit is IC via the resistor R3 connected to the positive pole of capacitor C2. Pin 5 is used during the start phase, that is, before the half-bridge inverter starts oscillating has taken up a voltage supply for the integrated circuit IC guaranteed.
- Pins 8 and 11 of the integrated circuit IC are used Using the capacitors C14 and C25 auxiliary voltages of 5 V and 15 V for the Microcontroller MC provided.
- the half-bridge inverter As long as the half-bridge inverter is oscillating, becomes the voltage for supplying the integrated circuit IC and the microcontroller MC by means of to the pin 7 of the integrated circuit IC and to the Center tap connected between the ignition capacitor C12 and the choke L4 Capacitor C13 and by means of an integrated in the integrated circuit IC Two-point controller derived from the load circuit.
- the structure of the microcontroller MC is shown schematically in FIG.
- the microcontroller MC has a clock, which is the working clock of the microcontroller determines a central processor unit, a program memory, a data memory and a math unit to perform simple math Operations.
- the aforementioned parts of the microcontroller MC are in the Block diagram of Figure 2 represented by module A.
- Module A are the Assigned pins 1 and 2, 15 to 22 and 23 to 28. This is at pins 1 to 2 Quartz crystal B2 connected to control the clock.
- the working clock frequency of the microcontroller is 8 MHz.
- Module B is an interface that is used for Preparation of digital or analog data for communication with the Communication device DS is used.
- Module B is pins 5 and 6 of the microcontroller MC assigned.
- Module C is a 5V power supply, with the pins 11 and 12 of the microcontroller MC is connected to the capacitor C14 or to the ground potential GRD.
- Address and data bus D are all components of the microcontroller MC together connected.
- the first control module E and the pins 3, 4 and 9 assigned to it of the microcontroller MC is used to control the transistor V1 of the step-up converter.
- the second control module G and the pins 7, 8 and 10 of it assigned to it Microcontroller MC is used to control transistors V2 and V3 of the half-bridge inverter as well as to control the transistor V4 of the heating device.
- Both control modules E, G are connected to one another via the data bus F.
- at module H is a 15V voltage source, which is connected via pins 13, 14 of the microcontroller MC with the ground potential GRD or with the capacitor C25 is connected.
- control module G The structure of the control module G is shown schematically in the block diagram in FIG.
- the control module G has the controllable current source SQ1, the controllable current sink SS1, the read-write memory DR1, DR2, the switch US1 for alternately switching the controllable current source and current sink on and off, the frequency divider FT1 for halving the frequency of the switchover signal of the switch US1, the data memory DR3 for storing the control signals for the transistors V2, V3, the reference current source IR for specifying a reference current I Ref that is as constant as possible for the controllable current source SQ1 and current sink SS1 and logic circuit components O1-O3, U1 -U6 on.
- a constant output voltage of 2 V is provided at pin 7 of the microcontroller MC, which, according to Ohm's law, allows a constant reference current I Ref to flow through the resistor R30.
- the value of this reference current I Ref can be predetermined by the choice of the resistance value of the resistor R30.
- the linear working range of the reference current I Ref extends from 5 ⁇ A to 50 ⁇ A.
- Capacitor C27 which serves as an electrical charge store, is connected to pin 8 of microcontroller MC. The capacitor C27 is charged with the aid of the controllable current source SQ1.
- the controllable current source SQ1 is switched off by the switch US 1 and the controllable current sink which discharges the capacitor C27 is switched on. If the voltage drop across the capacitor C27 reaches the value of 1.5 V, the controllable current sink SS1 is switched off by the switch US1 and the controllable current source SQ1 is switched on again, which charges the capacitor again to a voltage value of 3 V. In this way, the capacitor C27 is charged and discharged alternately. The voltage drop across the capacitor C27 therefore oscillates continuously between the values 1.5 V and 3 V.
- the controllable current source SQ1 and the controllable current sink SS1 and the switch US1 form a device for alternately charging and discharging the capacitor C27.
- the charging current for the capacitor C27 generated by the controllable current source SQ1 can be set by means of the read / write memory DR1.
- the read-write memory DR1 is a 16-bit data register, 12 bits of which are used to control the current source SQ1.
- the charging current for the capacitor C27 can therefore be set with a resolution of 12 bits between the values I Ref / 256 and 32 I Ref , the abbreviation I Ref standing for the reference current intensity of the reference current source IR.
- the entry in the data register DR1 determines the charging current for the current or subsequent charging process on the capacitor C27 and thus the time period that is required for this charging process.
- the discharge current of the capacitor C27 generated by the controllable current sink SS1 can be set by means of the read / write memory DR2.
- the random access memory DR2 is an 8 bit data register.
- the discharge current of the capacitor C27 can therefore be set with a resolution of 8 bits between the values 0.25 I Ref and 128 I Ref .
- the entry in the data register DR2 determines the discharge current for the current or subsequent discharge process on the capacitor C27 and thus the time period which is required for this discharge process.
- the oscillations of the state of charge of the capacitor C27 and the voltage drop across the capacitor C27 are therefore independent of the operating clock frequency of the microcontroller MC.
- the switch signals of the switch US1 are evaluated by the frequency divider FT1 and the AND gates U1, U2 to generate control signals for the transistors V2, V3 of the half-bridge inverter.
- the frequency divider FT1 only detects the switching pulses of the switch US1, which start a new charging process of the capacitor C27, and switches its two outputs, which are each connected to the input of an AND gate U1 or U2, alternately to "high” with each such switching pulse "or” Low “.
- the switch signals of the switch US1, on the other hand are also fed directly to the input of the AND gates U1, U2.
- the status register SR1 contains a status bit for activating and deactivating the control signals for the transistor V2 and a status bit for activating and deactivating the control signals for the transistor V3.
- the status of the status bit for activating and deactivating the control signals for the transistor V2 is monitored by the AND gate U2, while the status of the status bit for the transistor V3 is detected by the AND gate U1.
- the output states of the AND gate U1 and U2 are each stored in a bit of the data register DR3 and can be called up via the address and data bus D at the pins 23 and 24 of the microcontroller MC.
- the output states of the AND gates U1 or U2 are the driver circuits for controlling the gate electrode of the transistor V3 or V2 communicated.
- the frequency of the half-bridge inverter that is to say the switching cycle of its transistors V2, V3, is controlled by the duration of the individual charging and discharging processes of the capacitor C27. This situation will be explained in more detail below with the aid of diagrams a) to e) in FIG.
- the triangular curve in diagram a) shows the time course of the voltage drop on capacitor C27.
- the voltage drop across capacitor C27 varies linear with the time between the values 1.5 V and 3 V.
- Diagram b) shows the time course of the charging current for the capacitor C27.
- the charging current can differ according to the explanations above for the controllable current source SQ1 4096 take discrete values.
- diagram c) is the time course of the Discharge current shown for the capacitor C27.
- the discharge current can be according to the above explanations for controllable current sink SS1 256 different discrete Accept values.
- Diagram d) shows the time course of the pin 23 of the microcontroller MC callable control signal LG for the driver circuit of the Transistor V3.
- the diagram e) shows the time course of the on pin 24 of the Microcontroller MC retrievable control signal HG for the driver circuit of the Transistor V2.
- the duration of the individual charging processes on capacitor C27 is determined by the level of the charging current IL1.
- the duration of the individual discharge processes on the capacitor is analogous to this C27 is determined by the level of the discharge current IE1.
- the greater the discharge current IE1, the shorter the time it takes to discharge the capacitor from 3 V to 1.5 V is required.
- both control signals LG and HG take the logic state "Low” on. This means that the transistor V2 or V3 is switched on as long as the control signal HG or LG assigned to it has the state "high”.
- the Transistors V2, V3 of the half-bridge inverter become alternating in this way on and off. During the discharge of the capacitor C27 both transistors V2, V3 are switched off. The evaluation of the The voltage curve at the capacitor C27 thus enables frequency-modulated Control of the half-bridge inverter.
- the values for the charging current IL1 and the discharging current IE1 are given in the Data register DR1 or DR2 stored data set. This data will with the help of module A program-controlled depending on the on pin 18 of the Microcontrollers MC detected half wave of the AC component of the current in the Load circuit and determined by the current detected at pin 19 through transistor V3. Module A of the MC microcontroller calculates from the Comparison of the above-mentioned operating parameters with predefined setpoint values for controlling the controllable current source SQ1 and the controllable current sink SS1, which are stored in the data registers DR1 and DR2. To this Way for the frequency-modulated control of the half-bridge inverter in Depending on its operating parameters and the specified setpoints Control loop implemented.
- the setpoints for frequency modulated control of the Half-bridge inverters are program-controlled by module A of the microcontroller MC determines, for example depending on external control commands for dimming the lamps LP1, LP2 via the interfaces J3, J4 of the communication device DS communicated and fed to pin 5 of the microcontroller MC become.
- the data registers DR1 to DR4 and the status register SR1 are included connected to the address and data bus D. ,
- the voltage curve across capacitor C27 shown in diagram a) of FIG. 5 is also used to generate pulse width modulated control signals for the Transistor V4 of the heating device for the electrode filaments E1-E4 of the lamps LP1, LP2 evaluated.
- the 8-bit data register is used for this purpose Read-write memory DR4, the comparator K1, its inverting input the voltage drop across the capacitor C27 is detected and its non-inverting Input controlled by the data register DR4, the status register SR1 and the logic circuit components O1, 02, U3, U4, U5, 03 and the Driver circuit TR1 for the transistor V4.
- the comparator K1 compares that Voltage curve on capacitor C27 with that stored in data register DR4 Control value for the regulation of the heating current.
- the above manipulated variable is with a resolution of 8 bits can be varied.
- the voltage at the non-inverting is also corresponding Input of the comparator K1 with the same resolution in the range variable from 1.5 V to 3 V.
- the output signal of the comparator K1 is via the OR gate O1 and the AND gate U3 supplied to the OR gate 03, the Output is connected to the input of the driver circuit TR1, which is via the pin 10 of the microcontroller MC and the resistor R26 the gate electrode of the transistor V4 activated.
- the output signal of the comparator K1 is also also fed to the OR gate 02, the output of which with the AND gates U1 and U2 connected is.
- the output of the AND gate U1 is also via the AND gate U3 connected to the OR gate 03.
- the output of the AND gate U2 is over that AND gate U4 connected to the OR gate 03.
- the 8 bit status register SR1 has a first status bit for activating or deactivating a maximum heating current, that via the OR gate O1, the AND gate U3 with the OR gate 03 is connected. Maximum heating current means that the duty cycle of the transistor V4 is the duty cycle of transistor V2 or V3.
- the second status bit of the status register SR1, which is connected to the OR gate via the AND gate U3 03 is connected to activate or deactivate synchronous switching on of transistors V3 and V4.
- the third status bit of the status register SR1, the is connected to the OR gate 03 via the AND gate U4, is used for activation or deactivate the synchronous switching on of the transistors V2 and V4.
- the fourth status bit of the status register SR1 is connected to the AND gate U6, whose output is connected to the control module E via the data bus F. Since the Output of the AND gate U1 connected to the AND gate U6 is through the fourth status bit activates the connection of the control signal LG to the control module E. or deactivated.
- the fifth status bit of the status register SR1 is over the AND gate U5 connected to the OR gate 03.
- the AND gate U5 receives an input signal from the control module E via the data bus F. By the fifth status bit is the synchronization of the control signals for the transistors V1 and V4 can be activated or deactivated.
- the sixth status register status bit SR1 which is connected to the OR gate 02, is used to activate or deactivate the pulse width modulation of the control signals LG and HG.
- the seventh or Eighth status bit which is connected to the AND gate U1 or U2, is used for activation or deactivate the control signals LG or HG for the transistors V3 or V2 and for the transistor V4.
- the seventh or eighth status bit can be used to switch off in a simple manner the half-bridge inverter and the heating device for defective lamps LP1, LP2 can be performed.
- the diode D9 and the corresponding secondary winding of the transformer L3 realizes a direct current path in which the electrode coils E1 and E3 are connected in series. If one of the lamps LP1, LP2 is missing, this is the direct current path interrupted.
- the current in the resistor R14 DC path monitored on pin 25 of the MC microcontroller. Is the aforementioned DC path interrupted, can be reset by resetting the seventh or eighth Status bits of the status register SR1, the control signal LG or HG switched off and the Half-bridge inverters are thereby shut down.
- the electrode coil E2 or E4 breaks via the corresponding winding of the transformer L5 and the resistor R16 or R15 on pin 16 or 15 detected by the microcontroller MC. Moreover is on pins 15 and 16 of the microcontroller MC by means of the voltage divider resistors R15, R21 or R16, R20 the current through the lamp LP1 or LP2 or the voltage drop across the coupling capacitor C15 or C16 is monitored in order to the rectification effect that occurs at the end of the life of the lamp LP1 or LP2 the lamp LP1 or LP2 to detect. The information is from the microcontroller MC evaluated and can be via pin 6 and the communication device DS to be transmitted to an external control device or to control the Transistors V2, V3 and V4 are used.
- the transistor V4 always switched on synchronously with the transistor V2 of the half-bridge inverter becomes.
- the switch-on time or the switch-off time of the transistor T4 and thus also the pulse width of the control signal HTG depend on the output signal of the comparator K1 from which the manipulated value stored in the data register DR4 for the regulation of the heating current with the instantaneous voltage drop across the capacitor C27 compares. Reached during capacitor C27 charging at which the control signal HTG is in the "high” state, the voltage at Capacitor C27 changes the value stored in data register DR4 Control signal HTG from the "high” state to the "low” state.
- the pulse width of the control signal HTG is smaller or equal to the pulse width of the control signal HG.
- the duty cycle of the Transistor V4 is a maximum of as long as the duty cycle of transistor V2.
- the greatest possible heating current flows through the electrode coils E1-E4.
- the RC element is used R23, C18 at pin 17 the current through the transistor T4 or through the primary winding of the transformer L3 monitored and program controlled by means of the Module A compared with a target value and depending on the comparison a manipulated variable for generating the control signal HTG is stored in the data register DR4.
- the heating current required depends on the operating status of the lamps LP1, LP2. A relatively high heating current is required during the preheating phase, to enable a gentle ignition of the gas discharge. Besides that is too a heating current for the electrode filaments in strongly dimmed lamps LP1, LP2 necessary.
- FIG. 6 schematically shows the structure of the control module E for controlling the transistor V1 of the step-up converter, which is used to supply the DC voltage to the half-bridge inverter connected downstream.
- the control module E has the controllable current source SQ2, the controllable current sink SS2, the read / write memories DR5, DR6, DR7, the status registers SR1, SR2, SR3, the comparators K2, K3, K4, K5 and the driver circuit TR2 for the transistor V1 on.
- the aforementioned components of the control module E are networked with one another by logic circuit components.
- the status register SR1 is the same status register that has already been described in connection with the control module G.
- the controllable current source SQ2 serves to charge the capacitor C26 connected to the pin 9 of the microcontroller MC and the controllable current sink SS2 serves to discharge the capacitor C26.
- the controllable current source SQ2 and the controllable current sink SS2 are each coupled to the reference current source IR.
- the charging current and the discharging current for the capacitor C26 can each be set with a resolution of 8 bits between the values 0.25 I Ref and 128 I Ref .
- the charging current is set by means of the data register DR6 and the discharge current is set by means of DR5.
- Activating and deactivating the controllable power source SQ2 and the controllable Current sink SS2 for alternately charging and discharging the capacitor C26 is using the RS flip-flop FL1 and by means of the comparators K2 and K4 or alternatively carried out by means of the comparators K3 and K4.
- the comparator K2 compares the voltage across capacitor C26 to the upper voltage value while the comparator K4 the voltage on the capacitor C26 with the lower voltage value of 1.5 V.
- the upper voltage value is by means of the 8 bit data register DR7, which is connected to the inverting input of the comparator K2 is adjustable.
- the comparator K3 can also be used be chosen to match the voltage across capacitor C26 with the upper voltage value to compare.
- the voltage value is 3 V and cannot be varied.
- To control the controllable current source SQ2 and the controllable current sink SS2 for each other alternating charging and discharging processes on capacitor C26 are the outputs the comparators K2 and K3 via the positive edge generator FG1, the AND gate U7 and the OR gate 04 or via the positive edge generator FG2, the AND gate U8 and the OR gate 04 with the set input of the RS flip-flop FL1 connected.
- the output of the comparator K4 is via the positive edge generator FG3 connected to the reset input of the RS flip-flop FL1.
- the two outputs of the RS flip-flop FL1 are with the controllable current source SQ2 or connected to the controllable current sink SS2.
- the controllable Current source SQ2, the controllable current sink SS2, the comparators K2 (or K3) and K2 and the RS flip-flop FL1 form a device for alternating Charging and discharging a charge storage device, the capacitor C26 alternately charged with a charging current and a discharging current.
- the voltage on the capacitor C26 therefore oscillates continuously between the upper and lower voltage values. This oscillation is independent of the microcontroller's operating frequency MC.
- the control module E also has the comparator K5, the RS flip-flops FL3, FL4, the OR gate 07 and the status registers SR2, SR3 on.
- the status registers SR1-SR3 and the data registers DR5-DR7 are with the Address and data bus D connected. With the help of the RC element R32, C28 the Current through the transistor V1 on pin 3 of the microcontroller MC monitored. through the comparator K5, the OR gate 07 and the RS flip-flop FL4 Transistor V1 protected from excessive currents by the control signal PG for the Transistor V1 is turned off when an excessive current occurs.
- the purpose is pin 3 of the microcontroller MC with the non-inverting input of the comparator K5 connected, while at the inverting input of the comparator K5 a reference value is present, which has a resolution by means of the status register SR3 of 4 bits between the values 0 V to 2 V and the switch-off threshold defined for the control signal PG.
- the status register SR3 of 4 bits between the values 0 V to 2 V and the switch-off threshold defined for the control signal PG.
- the RS flip-flop FL4 is by means of the RS flip-flop FL3 set the first status bit of the status register SR2.
- the second status bit of the status register SR2 is dependent on the output signal of the OR gate 06 set or reset and indicates whether a control signal PG is present is or not.
- the remaining 6 bits of the status register SR2 are not used. Of the Status register SR3 are the first four bits to control the inverting Input of the comparator K5 used. The fifth bit of the status register SR3 enables additional control of the reference current source IR. The sixth bit of the status register SR3 is not used. Using the seventh bit of the status register SR3 and the AND gate U9 is the control signal for the driver circuit TR2 and the transistor V1 can be activated or deactivated. Using the eighth bit of the status register SR3 and the AND gate U7, U8 is optionally the output signal of the Comparator K2 or the comparator K3 can be activated. This will make two different ones Operating modes of the step-up converter enables.
- the step-up converter regulates not only the supply voltage of the half-bridge inverter, but also serves to correct the power factor.
- This mode of operation is used to operate discharge lamps, especially preferred by fluorescent lamps.
- the other mode of operation of the step-up converter is suitable for operating low-voltage halogen lamps on one electronic transformer, which has a step-up converter for regulating the supply voltage of the downstream inverter.
- the output signal of the comparator K2 is active.
- the Control signal PG can be via the AND gate U12, the data bus F and the AND gate U5 by means of the fifth status bit of the status register SR1 also on pin 10 of the Microcontroller MC can be made available to control the transistor V4.
- control signal LG of the control module G can be used to control the transistor V3 via the AND gate U6, the data bus F and the OR gate 07 by means of the fourth status bit of the status register SR1 also on pin 4 of the microcontroller MC for controlling the transistor V1 can be made available.
- the generation of the control signal PG for the Transistor V1 explained in more detail.
- the triangular curve in diagram a) of FIG. 7 represents the temporal voltage curve at capacitor C26.
- the step-shaped The curve in diagram a) of FIG. 7 represents the time course of the memory content of the data register DR7, which with a resolution of 8 bit values between Can accept 1.5 V and 3 V.
- diagram b) is the time course of the on the pin 4 of the microcontroller MC callable control signal PG for the gate electrode of the Transistor V1 shown.
- Diagram c) of FIG. 7 shows the course over time the generated by means of the RC element R32, C28 at pin 3 of the microcontroller MC Signal to monitor the current through transistor V1.
- FIG. d) is the time course of the charging current generated by the controllable current source SQ2 for the capacitor C26 and in diagram e) of FIG. 7, the time course of the Discharge current for the capacitor generated by the controllable current sink SS2 C26 shown.
- the capacitor C26 is alternately at an upper voltage value, which is determined by the memory content of the data register DR7 and discharge to a lower voltage of 1.5 V.
- the duration of the individual charging of the capacitor C26 is therefore determined by the upper voltage value and by means of the charging current which can be set by means of the data register DR6 IL2 set.
- the duration of the individual unloading processes is determined accordingly the upper voltage value and the one that can be set using the data register DR5 Discharge current IE2 determined.
- the periods of time for alternate loading and Discharging the capacitor C26 are required using the ones described above logic circuit components of the control module E for generating the frequency-modulated and pulse-width modulated control signal PG evaluated.
- the Comparison of the voltage curve across the capacitor shown in diagram a) C26 with the control signal PG shown in diagram b) shows that the transistor V1 turned off during capacitor C26 charging and during the discharge process on capacitor C26 is switched on. Does this happen at pin 3 of the microcontroller, signal IV1 (diagram c) of FIG. 7) detects the most inverting Input of the comparator K5 set threshold, so the control signal PG deactivated.
- the pin 20 of the microcontroller MC Voltage on capacitor C2 and on pin 21 of microcontroller MC the voltage monitored at capacitor C3.
- the module can be used to calculate these values
- a of the microcontroller MC calculate the current through the boost converter choke L2 and depending on these operating parameters can with the help of the Module A program the memory contents of the data register DR5, DR6 and DR7 determined for generating the control signal PG for the transistor V1 become. In this way, a control loop is used to control transistor V1 realized.
- the invention is not limited to the exemplary embodiments described in more detail above.
- the invention can also be used to control the switching transistors of ballasts for operating high-pressure discharge lamps and of electronic transformers for operating low-voltage halogen lamps be used.
Abstract
Description
- eine Vorrichtung zum abwechselnden Laden und Entladen eines mit dem Mikrocontroller verbindbaren oder in den Mikrocontroller integrierten Ladungsspeichers aufweist,
- Steuermittel für die Vorrichtung zum Steuern der Ladevorgänge und / oder der Entladevorgänge aufweist, und
- Auswertungsmittel aufweist, die dazu dienen, die zum Umladen des Ladungsspeichers zwischen unterschiedlichen Ladezuständen erforderlichen Zeitspannen auszuwerten und in Abhängigkeit davon ein Pulsweitenmodulationssteuersignal und / oder Frequenzsteuersignal zu erzeugen.
- eine Vorrichtung zum abwechselnden Laden und Entladen eines Ladungsspeichers,
- Steuermittel für die Vorrichtung zum abwechselnden Laden und Entladen des Ladungsspeichers, die zum Steuern der Ladevorgänge und / oder der Entladevorgänge dienen, und
- Auswertungsmittel auf, die dazu dienen, die Dauer der abwechselnden Lade- und Entladevorgänge des Ladungsspeichers auszuwerten und in Abhängigkeit davon ein Frequenzsteuersignal und/oder ein Pulsweitenmodulationssteuersignal zur Steuerung der Schaltmittel des Wechselrichters zu erzeugen.
- Figur 1
- Eine schematische Darstellung der ersten Hälfte der Schaltungsanordnung gemäß des bevorzugten Ausführungsbeispiels des erfindungsgemäßen Vorschaltgerätes
- Figur 2
- Eine schematische Darstellung der zweiten Hälfte der Schaltungsanordnung gemäß des bevorzugten Ausführungsbeispiels des erfindungsgemäßen Vorschaltgerätes
- Figur 3
- Ein Blockschaltbild des Mikrocontrollers
- Figur 4
- Ein Blockschaltbild des zweiten Steuermoduls G zur Steuerung des Halbbrückenwechselrichters und der Heizvorrichtung
- Figur 5
- Ein Diagramm der Steuersignale für den Wechselrichter und die Heizvorrichtung
- Figur 6
- Ein Blockschaltbild des ersten Steuermoduls E zur Steuerung des Hochsetzstellers
- Figur 7
- Ein Diagramm der Steuersignale für den Hochsetzsteller
Claims (35)
- Mikrocontroller mit mindestens einer Einrichtung (E, G) zur Pulsweitenmodulationssteuerung und/oder Frequenzsteuerung eines Schaltnetzteils, dadurch gekennzeichnet, dass die mindestens eine Einrichtung (E, G)eine Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines mit dem Mikrocontroller (MC) verbindbaren oder in den Mikrocontroller (MC) integrierten Ladungsspeichers (C27; C26) aufweist,Steuermittel für die Vorrichtung (SQ1, SS1; SQ2, SS2) zum Steuern der Ladevorgänge und / oder der Entladevorgänge aufweist, undAuswertungsmittel aufweist, die dazu dienen, die zum Umladen des Ladungsspeichers (C27; C26) zwischen unterschiedlichen Ladezuständen erforderlichen Zeitspannen auszuwerten und in Abhängigkeit davon ein Pulsweitenmodulationssteuersignal und / oder Frequenzsteuersignal zu erzeugen.
- Mikrocontroller nach Anspruch 1, dadurch gekennzeichnet, dass die Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers eine steuerbare Stromquelle (SQ1; SQ2) zum Beaufschlagen des Ladungsspeichers (C27; C26) mit einem einstellbaren Ladestrom und eine steuerbare Stromsenke (SS1; SS2) zum Beaufschlagen des Ladungsspeichers (C27; C26) mit einem einstellbaren Entladestrom aufweist.
- Mikrocontroller nach Anspruch 2, dadurch gekennzeichnet, dass die Einstellungen der steuerbaren Stromquelle (SQ1; SQ2) und der steuerbaren Stromsenke (SS1; SS2) in Bezug auf einen mittels einer Referenzstromquelle (IR) vorgebbaren Referenzstrompegel jeweils mit einer Auflösung von mindestens 8 Bit variierbar sind.
- Mikrocontroller nach Anspruch 3, dadurch gekennzeichnet, dass der Referenzstrompegel für den Lade- und den Entladestrom mittels eines ohmschen Widerstandes (R30) vorgebbar ist.
- Mikrocontroller nach Anspruch 1, dadurch gekennzeichnet, dass die Steuermittel für die Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers mindestens einen Schreib-Lese-Speicher (DR1, DR2; DR5, DR6) aufweisen.
- Mikrocontroller nach Anspruch 1, dadurch gekennzeichnet, dass die Steuermittel der Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers Schaltmittel (US1; FL1) aufweisen, die zum Umschalten der Vorrichtung (SQ1, SS1; SQ2, SS2) von Laden zu Entladen des Ladungsspeichers (C27; C26) bei Erreichen eines ersten Spannungswertes und zum Umschalten dieser Vorrichtung (SQ1, SS1; SQ2, SS2) von Entladen zu Laden des Ladungsspeichers (C27; C26) bei Erreichen eines zweiten, geringeren Spannungswertes dienen.
- Mikrocontroller nach Anspruch 6, dadurch gekennzeichnet, dass der erste Spannungswert oder zweite Spannungswert mittels eines Schreib-Lese-Speichers (DR7) einstellbar ist.
- Mikrocontroller nach einem oder mehreren der Ansprüche 1 bis 7, dadurch gekennzeichnet, dass ein Frequenzteiler (FT1) oder ein Impulsteiler vorgesehen ist, der an seinem Eingang das Umschalten der Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers von Entladen zu Laden oder von Laden zu Entladen detektiert und das Eingangssignal in Signale zur alternierenden Steuerung von abwechselnd schaltenden Schaltmitteln (V2, V3) des Schaltnetzteils aufteilt.
- Mikrocontroller nach einem oder mehreren der Ansprüche 1 bis 8, dadurch gekennzeichnet, dass der Mikrocontroller (MC) Schnittstellen (1-28) zur Erfassung externer Signale oder Daten besitzt und eine Einrichtung (A) zur Auswertung der externen Signale oder Daten und zur programmgesteuerten Ermittlung von Stellwerten zur Steuerung der Vorrichtung (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers aufweist.
- Schaltnetzteil mit mindestens einem steuerbaren Schaltmittel (V1; V2, V3) und mit einem Mikrocontroller (MC) nach einem oder mehreren der Ansprüche 1 bis 9 zur Erzeugung von Steuersignalen für das mindestens eine steuerbare Schaltmittel (V1; V2, V3).
- Vorschaltgerät zum Betrieb mindestens einer elektrischen Lampe (LP1, LP2), das einen Wechselrichter, mindestens einen an den Wechselrichter gekoppelten Lastkreis mit Anschlüssen (X1-X8) für die mindestens eine elektrische Lampe (LP1, LP2), eine Steuerschaltung zur Steuerung der Schaltmittel (V2, V3) des Wechselrichters und eine Gleichspannungsversorgungsschaltung für den Wechselrichter aufweist, wobei die Steuerschaltung einen Mikrocontroller (MC) mit einer Einrichtung (G) zur Pulsweitenmodulationssteuerung und / oder Frequenzsteuerung der Schaltmittel (V2, V3) des Wechselrichters umfasst,
dadurch gekennzeichnet, dass die Einrichtung (G) zur Pulsweitenmodulationssteuerung und / oder Frequenzsteuerungeine Vorrichtung (SQ1, SS1) zum abwechselnden Laden und Entladen eines Ladungsspeichers (C27) aufweist,Steuermittel für diese Vorrichtung (SQ1, SS1) zum Steuern der Ladevorgänge und / oder der Entladevorgänge aufweist, undAuswertungsmittel aufweist, die dazu dienen, die Dauer der abwechselnden Lade- und Entladevorgänge des Ladungsspeichers (C27) auszuwerten und in Abhängigkeit davon ein Frequenzsteuersignal und / oder ein Pulsweitenmodulationssteuersignal zur Steuerung der Schaltmittel (V2, V3) des Wechselrichters zu erzeugen. - Vorschaltgerät nach Anspruch 11, dadurch gekennzeichnet, dass ein Frequenzteiler (FT1) oder ein Impulsteiler vorgesehen ist, der an seinem Eingang das Umschalten der Vorrichtung (SQ1, SS1) zum abwechselnden Laden und Entladen eines Ladungsspeichers von Entladen zu Laden oder von Laden zu Entladen detektiert und das Eingangssignal in Signale zur alternierenden Steuerung der Schaltmittel (V2, V3) des Wechselrichters aufteilt.
- Vorschaltgerät nach Anspruch 11, dadurch gekennzeichnet, dass das Vorschaltgerät eine mit einem steuerbaren Schaltmittel (V4) ausgestattete Heizvorrichtung zum Beaufschlagen der Lampenelektroden (E1-E4) der mindestens einen elektrischen Lampe (LP1, LP2) mit einem Heizstrom aufweist und der Mikrocontroller (MC) einen Komparator (K1) aufweist, der den Ladezustand des Ladungsspeichers (C27) mit einem Referenzwert für die Lampenelektrodenheizung vergleicht und der zum Erzeugen eines Steuersignals zur Pulsweitenmodulation des steuerbaren Schaltmittels (V4) der Heizvorrichtung dient.
- Vorschaltgerät nach Anspruch 13, dadurch gekennzeichnet, dass der Referenzwert mittels eines Schreib-Lese-Speichers (DR4) einstellbar ist.
- Vorschaltgerät nach Anspruch 13, dadurch gekennzeichnet, dass der Mikrocontroller (MC) Synchronisationsmittel (SR1) zur Synchronisierung des steuerbaren Schaltmittels (V4) der Heizvorrichtung mit einem Schaltmittel (V2) des Wechselrichters aufweist.
- Vorschaltgerät nach Anspruch 11, dadurch gekennzeichnet, dassdie Gleichspannungsversorgungsschaltung einen Hochsetzsteller zur Leistungsfaktorkorrektur und / oder zum Erzielen einer möglichst sinusförmigen Netzstromentnahme aufweist,der Mikrocontroller (MC) eine zweite Vorrichtung (SQ2, SS2) zum abwechselnden Laden und Entladen eines zweiten Ladungsspeichers (C26) aufweist,der Mikrocontroller (MC) zweite Steuermittel für diese zweite Vorrichtung (SQ2, SS2) zum Steuern der Ladevorgänge und / oder der Entladevorgänge aufweist, undder Mikrocontroller (MC) zweite Auswertungsmittel aufweist, die dazu dienen, die zum Umladen des zweiten Ladungsspeichers (SQ2, SS2) zwischen unterschiedlichen Ladezuständen erforderlichen Zeitspannen auszuwerten und in Abhängigkeit davon ein Pulsweitenmodulationssteuersignal und/oder Frequenzsteuersignal für das steuerbare Schaltmittel (V1) des Hochsetzstellers zu erzeugen.
- Vorschaltgerät nach Anspruch 16, dadurch gekennzeichnet, dass die zweiten Auswertungsmittel einen ersten Komparator (K2, K3) zum Vergleich des Ladezustands des zweiten Ladungsspeichers (C26) mit einem ersten Spannungswert und einen zweiten Komparator (K4) zum Vergleich des Ladezustands des zweiten Ladungsspeichers (C26) mit einem zweiten, niedrigeren Spannungswert aufweisen, und dass die zweiten Steuermittel der zweiten Vorrichtung (SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers Schaltmittel (FL1) aufweisen, die zum Umschalten der zweiten Vorrichtung (SQ1, SS1; SQ2, SS2) von Laden zu Entladen des zweiten Ladungsspeichers (C26) bei Erreichen des ersten Spannungswertes und zum Umschalten der zweiten Vorrichtung (SQ2, SS2) von Entladen zu Laden des zweiten Ladungsspeichers (C26) bei Erreichen des zweiten, geringeren Spannungswertes dienen.
- Vorschaltgerät nach Anspruch 17, dadurch gekennzeichnet, dass der erste Spannungswert oder der zweite Spannungswert mittels eines Schreib-Lese-Speichers (DR7) einstellbar ist.
- Vorschaltgerät nach Anspruch 11 oder 16, dadurch gekennzeichnet, dass die Vorrichtungen (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers jeweils eine steuerbare Stromquelle (SQ1; SQ2) zum Beaufschlagen des Ladungsspeichers (C27) beziehungsweise des zweiten Ladungsspeichers (C26) mit einem einstellbaren Ladestrom und jeweils eine steuerbare Stromsenke (SS1; SS2) zum Beaufschlagen des Ladungsspeichers (C27) beziehungsweise des zweiten Ladungsspeichers (C26) mit einem einstellbaren Entladestrom aufweisen.
- Vorschaltgerät nach Anspruch 19, dadurch gekennzeichnet, dass die Einstellungen der steuerbaren Stromquellen (SQ1; SQ2) und der steuerbaren Stromsenken (SS1; SS2) in Bezug auf einen Referenzstrompegel (IR) jeweils mit einer Auflösung von mindestens 8 Bit variierbar sind.
- Vorschaltgerät nach Anspruch 20, dadurch gekennzeichnet, dass der Referenzstrompegel (IR) für den Ladestrom und den Entladestrom mittels eines ohmschen Widerstandes (R30) vorgebbar ist.
- Vorschaltgerät nach einem oder mehreren der Ansprüche 11 bis 21, dadurch gekennzeichnet, dass mindestens ein steuerbares Schaltmittel (V2, V3) des Wechselrichters und / oder das steuerbare Schaltmittel (V4) der Heizvorrichtung und / oder das steuerbare Schaltmittel (V1) des Hochsetzstellers über ein setz- und rücksetzbares Statusbit aktivierbar und deaktivierbar ist beziehungsweise sind.
- Vorschaltgerät nach einem oder mehreren der Ansprüche 11 bis 22, dadurch gekennzeichnet, dass der Mikrocontroller (MC) Schnittstellen (18, 19; 15, 16; 20, 21, 3) zur Erfassung von Betriebsparametern des Wechselrichters oder / und der mindestens einen elektrischen Lampe (LP1, LP2) oder / und des Hochsetzstellers besitzt und eine programmgesteuerte Einrichtung (A) aufweist, die zur Auswertung der Betriebsparameter und zur Ermittlung von Stellwerten für die Steuerung der Vorrichtungen (SQ1, SS1; SQ2, SS2) zum abwechselnden Laden und Entladen eines Ladungsspeichers und/oder zur Ermittlung des Referenzwertes für die Lampenelektrodenheizung und / oder zur Ermittlung des ersten oder zweiten Spannungswertes dient.
- Vorschaltgerät nach Anspruch einem oder mehreren der Ansprüche 11 bis 23, dadurch gekennzeichnet, dass das Vorschaltgerät Anschlüsse (J3, J4) und Mittel (DS) zur Kommunikation mit einer externen Steuervorrichtung besitzt und der Mikrocontroller (MC) Schnittstellen (5, 6) aufweist, die an die Anschlüsse (J3, J4) gekoppelt sind.
- Verfahren zum Betreiben mindestens einer elektrischen Lampe (LP1, LP2) mit Hilfe eines Vorschaltgerätes, das einen Wechselrichter mit einer einen Mikrocontroller (MC) enthaltenden Steuerschaltung für die Schaltmittel (V2, V3) des Wechselrichters aufweist und mindestens einen an den Wechselrichter gekoppelten Lastkreis mit Anschlüssen (X1-X8) für die mindestens eine elektrische Lampe (LP1, LP2) besitzt,
dadurch gekennzeichnet, dass mit Hilfe des Mikrocontrollers (MC)ein Ladungsspeicher (C27) abwechselnd mit einem Ladestrom und einem Entladestrom beaufschlagt wird,die Dauer der abwechselnden Lade- und Entladevorgänge des Ladungsspeichers (C27) ausgewertet wird und in Abhängigkeit davon ein Frequenzsteuersignal oder/und ein Pulsweitenmodulationssteuersignal zur alternierenden Steuerung der Schaltmittel (V2, V3) des Wechselrichters erzeugt wird. - Verfahren nach Anspruch 25, dadurch gekennzeichnet, dass das Umschalten von Entladen zu Laden des Ladungsspeichers (C27) oder von Laden zu Entladen des Ladungsspeichers (C27) detektiert wird und mittels eines Frequenzteilers (FT1) oder eines Impulsteilers Steuersignale zur alternierenden Steuerung der Schaltmittel (V2, V3) des Wechselrichters erzeugt werden.
- Verfahren nach Anspruch 25, dadurch gekennzeichnet, dass die Lampenelektroden (E1-E4) der mindestens einen elektrischen Lampe (LP1, LP2) mit einem Heizstrom beaufschlagt werden, wobei der Heizstrom mittels eines steuerbaren Schaltmittels (V4) geregelt wird, indem für das steuerbare Schaltmittel (V4) mit Hilfe eines Komparators (K1), der den Ladezustand des Ladungsspeichers (C27) mit einem Referenzwert für die Lampenelektrodenheizung vergleicht, pulsweitenmodulierte Steuersignale erzeugt werden.
- Verfahren nach Anspruch 27, dadurch gekennzeichnet, dass der Referenzwert in Abhängigkeit von der gewünschten Heizleistung eingestellt wird und in einem Schreib-Lese-Speicher (DR4) des Mikrocontrollers (MC) gespeichert wird.
- Verfahren nach Anspruch 27, dadurch gekennzeichnet, dass das steuerbare Schaltmittel (V4) zur Regelung des Heizstroms synchron mit einem Schaltmittel (V2) des Wechselrichters eingeschaltet wird und die Einschaltdauer des steuerbaren Schaltmittels (V4) zur Regelung des Heizstroms kleiner oder gleich der Einschaltdauer des Schaltmittels (V2) des Wechselrichters ist.
- Verfahren nach Anspruch 25, dadurch gekennzeichnet, dass die Gleichspannung zur Spannungsversorgung des Wechselrichters mittels eines Hochsetzstellers geregelt wird, um eine Leistungsfaktorkorrektur oder/und eine sinusförmige Netzstromentnahme zu gewährleisten, wobei Pulsweitenmodulationssteuersignale und / oder Frequenzsteuersignale für das steuerbare Schaltmittel (V1) des Hochsetzstellers mit Hilfe des Mikrocontrollers (MC) erzeugt werden, indem ein zweiter Ladungsspeicher (C26) zwischen unterschiedlichen Ladezuständen umgeladen wird und die Zeitspannen zum Umladen des zweiten Ladungsspeichers (C26) zur Erzeugung der Pulsweitenmodulationssteuersignale und / oder Frequenzsteuersignale für das steuerbare Schaltmittel (V1) des Hochsetzstellers ausgewertet werden.
- Verfahren nach Anspruch 30, dadurch gekennzeichnet, dass mit Hilfe eines ersten Komparators (K2, K3) der Ladezustand des zweiten Ladungsspeichers (C26) mit einem ersten Spannungswert verglichen wird und mit Hilfe eines zweiten Komparators (K4) der Ladezustand des zweiten Ladungsspeichers (C26) mit einem zweiten, niedrigeren Spannungswert verglichen wird, wobei bei Erreichen des ersten Spannungswertes der Ladevorgang des zweiten Ladungsspeichers (C26) beendet und der Entladevorgang des zweiten Ladungsspeichers (C26) gestartet wird, und wobei bei Erreichen des zweiten, niedrigeren Spannungswertes der Entladevorgang des zweiten Ladungsspeichers (C26) beendet und der Ladevorgang gestartet wird.
- Verfahren nach Anspruch 31, dadurch gekennzeichnet, dass der erste Spannungswert oder / und der zweite Spannungswert mittels eines Schreib-Lese-Speichers (DR7) eingestellt werden.
- Verfahren nach Anspruch 25 oder 30, dadurch gekennzeichnet, dass der Ladestrom mittels einer Stromquelle (SQ1; SQ2) generiert wird und die Stromstärke mittels eines Schreib-Lese-Speichers (DR1; DR6) eingestellt wird.
- Verfahren nach Anspruch 25 oder 30, dadurch gekennzeichnet, dass der Entladestrom mittels einer Stromsenke (SS1; SS2) generiert wird und die Stromstärke mittels eines Schreib-Lese-Speichers (DR2; DR5) eingestellt wird.
- Verfahren nach einem oder mehreren der Ansprüche 25 bis 34, dadurch gekennzeichnet, dass mit Hilfe des Mikrocontrollers (MC) Istwerte von Betriebsparametern des Wechselrichters und / oder der mindestens einen elektrischen Lampe (LP1, LP2) und/oder der Gleichspannungsversorgungsschaltung des Wechselrichters überwacht und zur Steuerung der Lade- bzw. Entladevorgänge der Ladungsspeicher (C27; C26) oder / und zur Bestimmung des Referenzwertes für die Lampenelektrodenheizung oder / und zur Bestimmung des ersten oder / und zweiten Spannungswertes ausgewertet werden.
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
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DE10102940A DE10102940A1 (de) | 2001-01-23 | 2001-01-23 | Mikrocontroller, Schaltnetzteil, Vorschaltgerät zum Betrieb mindestens einer elektrischen Lampe und Verfahren zum Betreiben mindestens einer elektrischen Lampe |
DE10102940 | 2001-01-23 |
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EP1227707A2 true EP1227707A2 (de) | 2002-07-31 |
EP1227707A3 EP1227707A3 (de) | 2005-01-12 |
EP1227707B1 EP1227707B1 (de) | 2007-09-05 |
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EP01129890A Expired - Lifetime EP1227707B1 (de) | 2001-01-23 | 2001-12-14 | Mikrocontroller, Schaltnetzteil und Vorschaltgerät zum Betrieb mindestens einer elektrischen Lampe |
Country Status (5)
Country | Link |
---|---|
US (1) | US6717374B2 (de) |
EP (1) | EP1227707B1 (de) |
AT (1) | ATE372659T1 (de) |
CA (1) | CA2368897A1 (de) |
DE (2) | DE10102940A1 (de) |
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US20020097008A1 (en) | 2002-07-25 |
EP1227707B1 (de) | 2007-09-05 |
DE10102940A1 (de) | 2002-08-08 |
EP1227707A3 (de) | 2005-01-12 |
US6717374B2 (en) | 2004-04-06 |
DE50112958D1 (de) | 2007-10-18 |
ATE372659T1 (de) | 2007-09-15 |
CA2368897A1 (en) | 2002-07-23 |
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